Modulation method and radio communication system

ABSTRACT

An input digital signal is periodically and alternately subjected to first modulation and second modulation, being thereby converted into a pair of a baseband I signal and a baseband Q signal. The first modulation and the second modulation are different from each other. The pair of the baseband I signal and the baseband Q signal are outputted. The first modulation may be at least 8-signal-point modulation while the second modulation may be phase shift keying.

CROSS REFERENCE OF RELATED APPLICATION

This application is a continuation of U.S. patent application Ser. No.09/240,632, filed Feb. 1, 1999.

BACKGROUND OF THE INVENTION

1. Field of the Invention

This invention relates to a modulation method. This invention alsorelates to a radio communication system.

2. Description of the Related Art

Japanese published unexamined patent application 9-93302 discloses adigital radio communication system in which a transmitted signal iscomposed of a stream of frames each having N successive symbols. Here, Ndenotes a predetermined natural number. In every frame, the first andsecond symbols are pilot symbols of known data (fixed data), and thepilot symbols are followed by (N-2) symbols representing maininformation to be transmitted.

In the digital radio communication system of Japanese application9-93302, since pilot symbols in every frame are composed of fixed dataand are not used in the transmission of main information, they cause adecrease in the main-information transmission rate.

SUMMARY OF THE INVENTION

It is a first object of this invention to provide a modulation methodwhich can prevent the occurrence of a decrease in an informationtransmission rate.

It is a second object of this invention to provide a radio communicationsystem which can prevent the occurrence of a decrease in an informationtransmission rate.

A first aspect of this invention provides a method of modulation whichcomprises the steps of periodically and alternately subjecting an inputdigital signal to first modulation and second modulation to convert theinput digital signal into a pair of a baseband I signal and a baseband Qsignal, the first modulation and the second modulation being differentfrom each other; and outputting the pair of the baseband I signal andthe baseband Q signal.

A second aspect of this invention is based on the first aspect thereof,and provides a method wherein the first modulation is at least8-signal-point modulation, and the second modulation is phase shiftkeying.

A third aspect of this invention is based on the second aspect thereof,and provides a method wherein the phase shift keying is quadrature phaseshift keying.

A fourth aspect of this invention is based on the third aspect thereof,and provides a method wherein the quadrature phase shift keying providessignal points on an I axis and a Q axis in an I-Q plane.

A fifth aspect of this invention is based on the second aspect thereof,and provides a method wherein the at least 8-signal-point modulation isat least 8 quadrature amplitude modulation.

A sixth aspect of this invention is based on the fourth aspect thereof,and provides a method wherein the at least 8-signal-point modulation isat least 8 quadrature amplitude modulation.

A seventh aspect of this invention is based on the fifth aspect thereof,and provides a method wherein the at least 8 quadrature amplitudemodulation is 16 quadrature amplitude modulation.

An eighth aspect of this invention is based on the sixth aspect thereof,and provides a method wherein the at least 8 quadrature amplitudemodulation is 16 quadrature amplitude modulation.

A ninth aspect of this invention is based on the fifth aspect thereof,and provides a method wherein the at least 8 quadrature amplitudemodulation provides signal points which result from rotation of signalpoints of at least 8-value normal quadrature amplitude modulationthrough an angle of π/4 radian about an origin in an I-Q plane.

A tenth aspect of this invention is based on the sixth aspect thereof,and provides a method wherein the at least 8 quadrature amplitudemodulation provides signal points which result from rotation of signalpoints of at least 8-value normal quadrature amplitude modulationthrough an angle of π/4 radian about an origin in an I-Q plane.

An eleventh aspect of this invention is based on the seventh aspectthereof, and provides a method wherein the 16 quadrature amplitudemodulation provides signal points which result from rotation of signalpoints of 16-value normal quadrature amplitude modulation through anangle of π/4 radian about an origin in an I-Q plane.

A twelfth aspect of this invention is based on the eighth aspectthereof, and provides a method wherein the 16 quadrature amplitudemodulation provides signal points which result from rotation of signalpoints of 16-value normal quadrature amplitude modulation through anangle of π/4 radian about an origin in an I-Q plane.

A thirteenth aspect of this invention is based on the second aspectthereof, and provides a method wherein a maximum of amplitudescorresponding to signal points of the at least 8-signal-point modulationin an I-Q plane is equal to an amplitude of a signal point of the phaseshift keying in the I-Q plane.

A fourteenth aspect of this invention is based on the seventh aspectthereof, and provides a method wherein a distance between signal pointsof the 16 quadrature amplitude modulation in an I-Q plane is equal to agiven value times a distance between signal points of the phase shiftkeying in the I-Q plane, the given value being in a range of 0.9 to 1.5.

A fifteenth aspect of this invention is based on the seventh aspectthereof, and provides a method wherein a distance between signal pointsof the 16 quadrature amplitude modulation in an I-Q plane is equal totwice a distance between signal points of the phase shift keying in theI-Q plane.

A sixteenth aspect of this invention is based on the eighth aspectthereof, and provides a method wherein a distance between signal pointsof the 16 quadrature amplitude modulation in the I-Q plane is equal to√{square root over (2)} times a distance between signal points of thequadrature phase shift keying in the I-Q plane.

A seventeenth aspect of this invention is based on the second aspectthereof, and provides a method wherein the phase shift keying providingperiodically-spaced symbols which represent corresponding portions ofthe input digital signal in terms of differences between phases of theperiodically-spaced symbols.

An eighteenth aspect of this invention is based on the seventeenthaspect thereof, and provides a method wherein the at least8-signal-point modulation assigns logic states of the input digitalsignal to respective signal points for a first symbol in response to asignal point used by a second symbol of the phase shift keying whichprecedes the first symbol.

A nineteenth aspect of this invention is based on the seventeenth aspectthereof, and provides a method wherein the at least 8-signal-pointmodulation is at least 8 quadrature amplitude modulation.

A twentieth aspect of this invention is based on the nineteenth aspectthereof, and provides a method wherein the at least 8 quadratureamplitude modulation is 16 quadrature amplitude modulation.

A twenty-first aspect of this invention is based on the nineteenthaspect thereof, and provides a method wherein the at least 8 quadratureamplitude modulation provides signal points which result from rotationof signal points of at least 8-value normal quadrature amplitudemodulation through an angle of π/4 radian about an origin in an I-Qplane.

A twenty-second aspect of this invention is based on the twentiethaspect thereof, and provides a method wherein the 16 quadratureamplitude modulation provides signal points which result from rotationof signal points of 16-value normal quadrature amplitude modulationthrough an angle of π/4 radian about an origin in an I-Q plane.

A twenty-third aspect of this invention is based on the seventeenthaspect thereof, and provides a method wherein the phase shift keying isquadrature phase shift keying.

A twenty-fourth aspect of this invention is based on the twenty-thirdaspect thereof, and provides a method wherein the quadrature phase shiftkeying provides signal points on an I axis and a Q axis in an I-Q plane.

A twenty-fifth aspect of this invention is based on the first aspectthereof, and provides a method wherein the first modulation is 16quadrature amplitude modulation, and the second modulation is quadraturephase shift keying.

A twenty-sixth aspect of this invention is based on the twenty-fifthaspect thereof, and provides a method wherein the 16 quadratureamplitude modulation provides signal points which result from rotationof signal points of 16-value normal quadrature amplitude modulationthrough an angle of π/4 radian about an origin in an I-Q plane.

A twenty-seventh aspect of this invention is based on the twenty-fifthaspect thereof, and provides a method wherein the quadrature phase shiftkeying provides signal points on an I axis and a Q axis in an I-Q plane.

A twenty-eighth aspect of this invention is based on the twenty-fifthaspect thereof, and provides a method wherein the 16 quadratureamplitude modulation provides signal points which result from rotationof signal points of 16-value normal quadrature amplitude modulationthrough an angle of π/4 radian about an origin in an I-Q plane, and thequadrature phase shift keying provides signal points on an I axis and aQ axis in the I-Q plane.

A twenty-ninth aspect of this invention is based on the twenty-fifthaspect thereof, and provides a method wherein a maximum of amplitudescorresponding to signal points of the 16 quadrature amplitude modulationin an I-Q plane is equal to an amplitude of a signal point of thequadrature phase shift keying in the I-Q plane.

A thirtieth aspect of this invention is based on the twenty-fifth aspectthereof, and provides a method wherein a distance between signal pointsof the 16 quadrature amplitude modulation in an I-Q plane is equal to agiven value times a distance between signal points of the quadraturephase shift keying in the I-Q plane, the given value being in a range of0.9 to 1.5.

A thirty-first aspect of this invention is based on the twenty-fifthaspect thereof, and provides a method wherein a distance between signalpoints of the 16 quadrature amplitude modulation in an I-Q plane isequal to twice a distance between signal points of the quadrature phaseshift keying in the I-Q plane.

A thirty-second aspect of this invention is based on the twenty-sixthaspect thereof, and provides a method wherein a distance between signalpoints of the 16 quadrature amplitude modulation in the I-Q plane isequal to √{square root over (2)} times a distance between signal pointsof the quadrature phase shift keying in the I-Q plane.

A thirty-third aspect of this invention provides a transmissionapparatus comprising first means for periodically and alternatelysubjecting an input digital signal to first modulation and secondmodulation to convert the input digital signal into a pair of a basebandI signal and a baseband Q signal, the first modulation and the secondmodulation being different from each other, the first modulation beingat least 8-signal-point modulation, the second modulation being phaseshift keying; and second means for outputting the pair of the baseband Isignal and the baseband Q signal.

A thirty-fourth aspect of this invention provides a reception apparatuscomprising first means for recovering a pair of a baseband I signal anda baseband Q signal from a received signal; and second means forperiodically and alternately subjecting the pair of the baseband Isignal and the baseband Q signal to first demodulation and seconddemodulation to convert the pair of the baseband I signal and thebaseband Q signal into an original digital signal; wherein the firstdemodulation is for signals of at least 8 signal points modulation, andthe second demodulation is phase shift keying demodulation.

A thirty-fifth aspect of this invention provides a radio communicationsystem comprising a transmission apparatus including a1) first means forperiodically and alternately subjecting an input digital signal to firstmodulation and second modulation to convert the input digital signalinto a pair of a baseband I signal and a baseband Q signal, the firstmodulation and the second modulation being different from each other,the first modulation being at least 8-signal-point modulation, thesecond modulation being phase shift keying; a2) second means forconverting the pair of the baseband I signal and the baseband Q signalgenerated by the first means into a corresponding RF signal; and a3)third means for transmitting the RF signal generated by the secondmeans; a reception apparatus including b1) fourth means for receivingthe RF signal transmitted by the third means; b2) fifth means forrecovering a pair of a baseband I signal and a baseband Q signal fromthe RF signal received by the fourth means; and b3) sixth means forperiodically and alternately subjecting the pair of the baseband Isignal and the baseband I signal recovered by the fifth means to firstdemodulation and second demodulation to convert the pair of the basebandI signal and the baseband Q signal into an original digital signal;wherein the first demodulation is for signals of at least 8 signalpoints modulation, and the second demodulation is phase shift keyingdemodulation.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of a transmitter in a radio communicationsystem according to a first embodiment of this invention.

FIG. 2 is a block diagram of a modulator (a quadrature basebandmodulator) in FIG. 1.

FIG. 3 is a block diagram of a receiver in the radio communicationsystem according to the first embodiment of this invention.

FIG. 4 is a block diagram of a quasi synchronous detector in FIG. 3.

FIG. 5 is a diagram of an arrangement of 16 signal points in an I-Qplane which are provided by 16-value APSK.

FIG. 6 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by QPSK.

FIG. 7 is a time-domain diagram of a symbol stream.

FIG. 8 is a bock diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa second embodiment of this invention.

FIG. 9 is a bock diagram of a quasi synchronous detector in a receiverin the radio communication system according to the second embodiment ofthis invention.

FIG. 10 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 2^(2m)QAM (2^(2m)-value QAM).

FIG. 11 is a time-domain diagram of a symbol stream.

FIG. 12 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 16QAM (16-value QAM).

FIG. 13 is a time-domain diagram of a symbol stream.

FIG. 14 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa fourth embodiment of this invention.

FIG. 15 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by QPSK.

FIG. 16 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the fourth embodiment ofthis invention.

FIG. 17 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa fifth embodiment of this invention.

FIG. 18 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the fifth embodiment ofthis invention.

FIG. 19 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa seventh embodiment of this invention.

FIG. 20 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the seventh embodiment ofthis invention.

FIG. 21 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 2^(2m)QAM (2^(2m)-value QAM).

FIG. 22 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 16QAM (16-value QAM).

FIG. 23 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa ninth embodiment of this invention.

FIG. 24 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the ninth embodiment ofthis invention.

FIG. 25 is a time-domain diagram of a symbol stream.

FIG. 26 is a diagram of the relation between the bit error rate and thecarrier-to-noise power ratio which is provided in an eleventh embodimentof this invention, and the corresponding relation in a prior-art system.

FIG. 27 is a diagram of the relation between the bit error rate and thecarrier-to-noise power ratio which is provided in a twelfth embodimentof this invention, and the corresponding relation in a prior-art system.

FIG. 28 is a diagram of the relation between the bit error rate and thecarrier-to-noise power ratio which is provided in a thirteenthembodiment of this invention, and the corresponding relation in aprior-art system.

FIG. 29 is a diagram of the relation between the bit error rate and thecarrier-to-noise power ratio which is provided in a fourteenthembodiment of this invention, and the corresponding relation in aprior-art system.

FIG. 30 is a block diagram of a transmitter in a radio communicationsystem according to a fifteenth embodiment of this invention.

FIG. 31 is a block diagram of a modulator (a quadrature basebandmodulator) in FIG. 30.

FIG. 32 is a block diagram of a receiver in the radio communicationsystem according to the fifteenth embodiment of this invention.

FIG. 33 is a block diagram of a quasi synchronous detector in FIG. 32.

FIG. 34 is a diagram of an arrangement of 8 signal points in an I-Qplane which are provided by 8PSK.

FIG. 35 is a diagram of an arrangement of two signal points in an I-Qplane which are provided by BPSK.

FIG. 36 is a time-domain diagram of a symbol stream.

FIG. 37 is a diagram of an arrangement of signal points of BPSK, andlogic states assigned thereto.

FIG. 38 is a diagram of signal points of 8PSK, logic states assignedthereto, and a first signal point of BPSK.

FIG. 39 is a diagram of signal points of 8PSK, logic states assignedthereto, and a second signal point of BPSK.

FIG. 40 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa sixteenth embodiment of this invention.

FIG. 41 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the sixteenth embodimentof this invention.

FIG. 42 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 2^(2m)QAM (2^(2m)-value QAM).

FIG. 43 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 16QAM (16-value QAM).

FIG. 44 is a time-domain diagram of a symbol stream.

FIG. 45 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a first signal point of BPSK.

FIG. 46 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a second signal point of BPSK.

FIG. 47 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa seventeenth embodiment of this invention.

FIG. 48 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the seventeenthembodiment of this invention.

FIG. 49 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 2^(2m)QAM (2^(2m)-value QAM).

FIG. 50 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by 16QAM (16-value QAM).

FIG. 51 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a first signal point of BPSK.

FIG. 52 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a second signal point of BPSK.

FIG. 53 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toan eighteenth embodiment of this invention.

FIG. 54 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the eighteenth embodimentof this invention.

FIG. 55 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by QPSK.

FIG. 56 is a time-domain diagram of a symbol stream.

FIG. 57 is a diagram of signal points of QPSK, and logic states assignedthereto.

FIG. 58 is a diagram of signal points of 8PSK, logic states assignedthereto, and a first signal point of QPSK.

FIG. 59 is a diagram of signal points of 8PSK, logic states assignedthereto, and a second signal point of QPSK.

FIG. 60 is a diagram of signal points of 8PSK, logic states assignedthereto, and a third signal point of QPSK.

FIG. 61 is a diagram of signal points of 8PSK, logic states assignedthereto, and a fourth signal point of QPSK.

FIG. 62 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa nineteenth embodiment of this invention.

FIG. 63 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the nineteenth embodimentof this invention.

FIG. 64 is a time-domain diagram of a symbol stream.

FIG. 65 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a first signal point of QPSK.

FIG. 66 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a second signal point of QPSK.

FIG. 67 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a third signal point of QPSK.

FIG. 68 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a fourth signal point of QPSK.

FIG. 69 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa twentieth embodiment of this invention.

FIG. 70 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the twentieth embodimentof this invention.

FIG. 71 is a diagram of an arrangement of signal points in an I-Q planewhich are provided by QPSK.

FIG. 72 is a diagram of signal points of 8PSK, logic states assignedthereto, and a first signal point of QPSK.

FIG. 73 is a diagram of signal points of 8PSK, logic states assignedthereto, and a second signal point of QPSK.

FIG. 74 is a diagram of signal points of 8PSK, logic states assignedthereto, and a third signal point of QPSK.

FIG. 75 is a diagram of signal points of 8PSK, logic states assignedthereto, and a fourth signal point of QPSK.

FIG. 76 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa twenty-first embodiment of this invention.

FIG. 77 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the twenty-firstembodiment of this invention.

FIG. 78 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a first signal point of QPSK.

FIG. 79 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a second signal point of QPSK.

FIG. 80 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a third signal point of QPSK.

FIG. 81 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a fourth signal point of QPSK.

FIG. 82 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa twenty-second embodiment of this invention.

FIG. 83 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the twenty-secondembodiment of this invention.

FIG. 84 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a first signal point of QPSK.

FIG. 85 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a second signal point of QPSK.

FIG. 86 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a third signal point of QPSK.

FIG. 87 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a fourth signal point of QPSK.

FIG. 88 is a block diagram of a modulator (a quadrature basebandmodulator) in a transmitter in a radio communication system according toa twenty-third embodiment of this invention.

FIG. 89 is a block diagram of a quasi synchronous detector in a receiverin the radio communication system according to the twenty-thirdembodiment of this invention.

FIG. 90 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a first signal point of QPSK.

FIG. 91 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a second signal point of QPSK.

FIG. 92 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a third signal point of QPSK.

FIG. 93 is a diagram of signal points of 16QAM (16-value QAM), logicstates assigned thereto, and a fourth signal point of QPSK.

FIG. 94 is a diagram of relations between the bit error rate and theratio of the 1-bit signal energy “Eb” to the noise power density “N0”.

DESCRIPTION OF THE PREFERRED EMBODIMENTS

In the following description, 2^(2m)-value QAM means 2^(2m)QAM, and16-value QAM means 16QAM and 16-value APSK means 16APSK.

First Embodiment

FIG. 1 shows a transmitter 10 in a radio communication system accordingto a first embodiment of this invention. With reference to FIG. 1, thetransmitter 10 includes a modulator 12 and an RF (radio frequency)portion 15. The modulator 12 is defined and referred to as thequadrature baseband modulator 12.

A digital signal to be transmitted (that is, an input digital signal ormain information to be transmitted) is fed to the quadrature basebandmodulator 12. The device 12 subjects the input digital signal toquadrature baseband modulation, thereby converting the input digitalsignal into a pair of modulation-resultant baseband signals, that is, abaseband I (in-phase) signal and a baseband Q (quadrature) signal. Thequadrature baseband modulator 12 outputs the baseband I signal and thebaseband Q signal to the RF portion 15.

The RF portion 15 converts the baseband I signal and the baseband Qsignal into an RF signal through frequency conversion which may includeRF modulation. The RF portion 15 feeds the RF signal to an antenna 17.The RF signal is radiated by the antenna 17.

As shown in FIG. 2, the quadrature baseband modulator 12 includes a16-value APSK (amplitude phase shift keying) modulator 12A, a QPSK(quadrature phase shift keying) modulator 12B, a reference signalgenerator 12C, and switches 12D and 12E.

The APSK modulator 12A and the GPSK modulator 12B receives the inputdigital signal. The device 12A subjects the input digital signal to16APSK (16-value APSK modulation), thereby converting the input digitalsignal into a pair of a baseband I signal and a baseband Q signal. TheAPSK modulator 12A outputs the baseband I signal to the switch 12D. TheAPSK modulator 12A outputs the baseband Q signal to the switch 12E. Thedevice 12B subjects the input digital signal to QPSK (QPSK modulation),thereby converting the input digital signal into a pair of a baseband Isignal and a baseband Q signal. The QPSK modulator 12B outputs thebaseband I signal to the switch 12D. The QPSK modulator 12B outputs thebaseband Q signal to the switch 12E. The reference signal generator 12Coutputs a reference baseband I signal to the switch 12D. The referencesignal generator 12C outputs a reference baseband Q signal to the switch12E. The output I and Q signals from the reference signal generator 12Care used in acquiring synchronization between the transmitter 10 and areceiver during an initial stage of signal transmission. The switch 12Dselects one of the output I signal from the APSK modulator 12A, theoutput I signal from the QPSK modulator 12B, and the output I signalfrom the reference signal generator 12C, and transmits the selected Isignal to the RF portion 15. The switch 12E selects one of the output Qsignal from the APSK modulator 12A, the output Q signal from the QPSKmodulator 12B, and the output Q signal from the reference signalgenerator 12C, and transmits the selected Q signal to the RF portion 15.

During an initial stage of signal transmission, the switch 12D selectsthe output I signal from the reference signal generator 12C while theswitch 12D selects the output Q signal from the reference signalgenerator 12C. During an interval of time which follows the initialstage, the switch 12D alternately selects one of the output I signalfrom the APSK modulator 12A and the output I signal from the QPSKmodulator 12B at a predetermined period, and transmits the selected Isignal to the RF portion 15. During the time interval following theinitial stage, the switch 12E alternately selects one of the output Qsignal from the APSK modulator 12A and the output Q signal from the GPSKmodulator 12B at the predetermined period, and transmits the selected Qsignal to the RF portion 15.

Accordingly, with respect to the input digital signal, the quadraturebaseband modulator 12 alternately implements the 16-value APSKmodulation and the QPSK modulation at the predetermined period.

FIG. 3 shows a receiver 20 in the radio communication system accordingto the first embodiment of this invention. With reference to FIG. 3, thereceiver 20 includes an RF portion 22, calculators 25 and 26, and aquasi synchronous detector 29.

An RF signal caught by an antenna 21 is applied to the RF portion 22.The RF portion 22 subjects the applied RF signal to frequency conversion(which may include RF demodulation), thereby converting the applied RFsignal into a pair of a baseband I signal and a baseband Q signal. TheRF portion 22 outputs the baseband I signal and the baseband Q signal tothe calculators 25 and 26, and the quasi synchronous detector 29.

The calculator 25 estimates an amplitude distortion amount from thebaseband I signal and the baseband Q signal. The calculator 25 informsthe quasi synchronous detector 29 of the estimated amplitude distortionamount. The calculator 26 estimates a frequency offset amount from thebaseband I signal and the baseband Q signal. The calculator 26 informsthe quasi synchronous detector 29 of the estimated frequency offsetamount.

The device 29 subjects the baseband I signal and the baseband Q signalto quasi synchronous detection responsive to the estimated amplitudedistortion amount and the estimated frequency offset amount, therebydemodulating the baseband I signal and the baseband Q signal into anoriginal digital signal. Thus, the quasi synchronous detector 29recovers the original digital signal from the baseband I signal and thebaseband Q signal. The quasi synchronous detector 29 outputs therecovered original digital signal.

As shown in FIG. 4, the quasi synchronous detector 29 includes a16-value APSK demodulator 29A, a QPSK demodulator 29B, and a switch 29C.

The APSK demodulator 29A and the QPSK demodulator 29B receive thebaseband I and Q signals from the RF portion 22. In addition, the APSKdemodulator 29A and the QPSK demodulator 29B are informed of theestimated amplitude distortion amount and the estimated frequency offsetamount by the calculators 25 and 26.

The device 29A subjects the baseband I signal and the baseband Q signalto 16-value APSK demodulation responsive to the estimated amplitudedistortion amount and the estimated frequency offset amount, therebydemodulating the baseband I signal and the baseband Q signal into anoriginal digital signal. Thus, the APSK demodulator 29A recovers theoriginal digital signal from the baseband I signal and the baseband Qsignal. The APSK demodulator 29A outputs the recovered original digitalsignal to the switch 29C.

The device 29B subjects the baseband I signal and the baseband Q signalto QPSK demodulation responsive to the estimated amplitude distortionamount and the estimated frequency offset amount, thereby demodulatingthe baseband I signal and the baseband Q signal into an original digitalsignal. Thus, the QPSK demodulator 29B recovers the original digitalsignal from the baseband I signal and the baseband Q signal. The QPSKdemodulator 29B outputs the recovered original digital signal to theswitch 29C.

The switch 29C alternately selects the output digital signal from theAPSK demodulator 29A and the output digital signal from the QPSKdemodulator 29B in response to a timing signal (a frame and symbol syncsignal), and transmits the selected digital signal to a later stage.When the baseband I and Q signals outputted from the RF portion 22 tothe quasi synchronous detector 29 correspond to a result of the 16-valueAPSK modulation, the switch 29C selects the output digital signal fromthe APSK demodulator 29A. When the I and Q signals outputted from the RFportion 22 to the quasi synchronous detector 29 correspond to a resultof the QPSK modulation, the switch 29C selects the output digital signalfrom the QPSK demodulator 29B.

For example, the APSK demodulator 29A includes an amplitude correctioncircuit (an amplitude compensation circuit) and a frequency correctioncircuit (a frequency compensation circuit). The amplitude correctioncircuit compensates for an amplitude distortion of the baseband I signaland the baseband Q signal in response to the estimated amplitudedistortion, thereby generating a first compensation-resultant baseband Isignal and a first compensation-resultant baseband Q signal. Thefrequency correction circuit compensates for a frequency offset of thefirst compensation-resultant baseband I signal and the firstcompensation-resultant baseband Q signal in response to the estimatedfrequency offset amount, thereby generating a secondcompensation-resultant baseband I signal and a secondcompensation-resultant baseband Q signal. In the APSK demodulator 29A,the second compensation-resultant baseband I signal and the secondcompensation-resultant baseband Q signal are subjected to the 16-valueAPSK demodulation, being converted into the original digital signal.

For example, the QPSK demodulator 29B includes an amplitude correctioncircuit and a frequency correction circuit. The amplitude correctioncircuit compensates for an amplitude distortion of the baseband I signaland the baseband Q signal in response to the estimated amplitudedistortion, thereby generating a first compensation-resultant baseband Isignal and a first compensation-resultant baseband Q signal. Thefrequency correction circuit compensates for a frequency offset of thefirst compensation-resultant baseband I signal and the firstcompensation-resultant baseband Q signal in response to the estimatedfrequency offset amount, thereby generating a secondcompensation-resultant baseband I signal and a secondcompensation-resultant baseband Q signal. In the QPSK demodulator 29B,the second compensation-resultant baseband I signal and the secondcompensation-resultant baseband Q signal are subjected to the QPSKdemodulation, being converted into the original digital signal.

FIG. 5 shows an arrangement of 16 signal points in an I-Q plane whichare provided by the 16-value APSK modulation. In FIG. 5, the 16 signalpoints are denoted by the reference numeral “101”. The 16 signal pointsare assigned to 16 different logic values respectively. The positions(I_(16APSK), Q_(16APSK)) of the 16 signal points are given by thefollowing equations.

$\begin{matrix}{I_{16{APSK}} = {{h\; 0\left\{ {{{\cos\left( \frac{\pi}{8} \right)}{\cos\left( \frac{k\;\pi}{4} \right)}} - {{\sin\left( \frac{\pi}{8} \right)}{\sin\left( \frac{k\;\pi}{4} \right)}}} \right\}} + {h\; 1{\cos\left( \frac{k\;\pi}{4} \right)}}}} & (1) \\{Q_{16{APSK}} = {{h\; 0\left\{ {{{\cos\left( \frac{\pi}{8} \right)}{\sin\left( \frac{k\;\pi}{4} \right)}} + {{\sin\left( \frac{\pi}{8} \right)}{\cos\left( \frac{k\;\pi}{4} \right)}}} \right\}} + {h\; 1{\sin\left( \frac{k\;\pi}{4} \right)}}}} & (2)\end{matrix}$where “k” denotes a variable integer; (h0, h1)=(0, g1) or (h0, h1)=(g0,0); “g0” and “g1” denote predetermined constants respectively; and theconstant g1 is greater than the constant g0. With reference to FIG. 5,the signal points on the Q axis correspond to the maximum amplitudewhich is given by the constant g1.

FIG. 6 shows an arrangement of signal points in an I-Q plane which areprovided by the QPSK modulation. In FIG. 6, the signal points aredenoted by the reference numeral “201”. The signal points are assignedto different logic values respectively. The positions (I_(QPSK),Q_(QPSK)) of the signal points are given by the following equations.

$\begin{matrix}{I_{QPSK} = {p\left\{ {{{\cos\left( \frac{\pi}{4} \right)}{\cos\left( \frac{k\;\pi}{2} \right)}} - {{\sin\left( \frac{\pi}{4} \right)}{\sin\left( \frac{k\;\pi}{2} \right)}}} \right\}}} & (3) \\{Q_{QPSK} = {p\left\{ {{{\cos\left( \frac{\pi}{4} \right)}{\sin\left( \frac{k\;\pi}{2} \right)}} + {{\sin\left( \frac{\pi}{4} \right)}{\cos\left( \frac{k\;\pi}{2} \right)}}} \right\}}} & (4)\end{matrix}$where “k” denotes a variable integer, and “p” denotes a predeterminedconstant. With reference to FIG. 6, all the signal points correspond toa same amplitude given by the constant “p”. In addition, all thedistances between the neighboring signal points are equal to a samevalue given by √{square root over (2)}. Furthermore, the signal pointsare spaced at equal angular intervals. Accordingly, a QPSKmodulation-resultant signal is suited for detecting an amplitudedistortion and a frequency offset.

With reference to FIG. 7, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator 12 in the transmitter10, or the RF signal outputted from the RF portion 15 in the transmitter10 is composed of a stream of frames each having N successive symbols.Here, N denotes a predetermined natural number. In every frame, thefirst symbol results from the QPSK modulation, and the second and latersymbols result from the 16-value APSK modulation. The first symbol inevery frame (that is, the QPSK symbol in every frame) is used by thereceiver 20 as a pilot symbol for estimating an amplitude distortionamount and a frequency offset amount. It should be noted that everypilot symbol also carries a part of the main information to betransmitted.

In the receiver 20, the calculator 25 separates pilot symbols (firstsymbols in frames) from the output I and Q signals of the RF portion 22in response to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 25 estimates an amplitudedistortion amount from the separated pilot symbols. Similarly, thecalculator 26 separates pilot symbols (first symbols in frames) from theoutput I and Q signals of the RF portion 22 in response to a signal (aframe and symbol sync signal) having a period corresponding to Nsymbols. The calculator 26 estimates a frequency offset amount from theseparated pilot symbols.

Preferably, the maximum amplitude g1 provided by the 16-value APSKmodulation is equal to the amplitude “p” provided by the QPSKmodulation. In this case, the amplitude distortion amount and thefrequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver 20 is designed toimplement the following processes. The quasi synchronous detector 29subjects the output I and Q signals of the RF portion 22 to the QPSKdemodulation and outputs the GPSK-demodulation resultant digital signalwhen the output I and Q signals of the RF portion 22 represent a pilotsymbol. The quasi synchronous detector 29 subjects the output I and Qsignals of the RF portion 22 to the 16-value APSK demodulation andoutputs the APSK-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 22 represent a normal symbol differentfrom a pilot symbol.

Second Embodiment

A second embodiment of this invention is similar to the first embodimentthereof except for design changes indicated hereinafter.

As shown in FIG. 8, a modulator (a quadrature baseband modulator) in atransmitter in the second embodiment of this invention includes a2^(2m)QAM (2^(2m)-value QAM or 2^(2m)-value quadrature amplitudemodulation) modulator 12F instead of the 16-value APSK modulator 12A(see FIG. 2). Here, “m” denotes a predetermined integer equal to orgreater than “2”.

As shown in FIG. 9, a quasi synchronous detector in a receiver in thesecond embodiment of this invention includes a 2^(2m)-value QAMdemodulator 29D instead of the 16-value APSK demodulator 29A (see FIG.4).

FIG. 10 shows an arrangement of signal points in an I-Q plane which areprovided by 2^(2m)-value QAM executed in the QAM modulator 12F. In FIG.10, the signal points are denoted by the reference numeral “401”. Thesignal points are assigned to different logic values respectively. Thepositions (I_(QAM), Q_(QAM)) of the signal points are given by thefollowing equations.I _(QAM) =q(2^(m-1) a1+2^(m-2) a2+ ••• +2⁰ am)  (5)Q _(QAM) =q(2^(m-1) b1+2^(m-2) b2+ ••• +2⁰ bm)  (6)where “m” denotes a predetermined integer equal to or greater than “2”;(a1, b1), (a2, b2), . . . , (am, bm) are binary code words of “1” and“−1”; and “q” denotes a predetermined constant. With reference to FIG.10, specified ones of the signal points correspond to the maximumamplitude which is given as follows.(2^(m-1)+2^(m-2)+ ••• +2⁰)√{square root over (2)}q  (7)

With reference to FIG. 11, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator in the transmitter (seeFIG. 1), or the RF signal outputted from the RF portion in thetransmitter is composed of a stream of frames each having N successivesymbols. Here, N denotes a predetermined natural number. In every frame,the first symbol results from the QPSK modulation, and the second andlater symbols result from the 2^(2m)-value QAM. The first symbol inevery frame (that is, the QPSK symbol in every frame) is used by thereceiver as a pilot symbol for estimating an amplitude distortion amountand a frequency offset amount. It should be noted that every pilotsymbol also carries a part of the main information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 2^(2m)-value QAM, thatis, the value given by the expression (7), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 22 represent a normal symbol differentfrom a pilot symbol.

Third Embodiment

A third embodiment of this invention is similar to the second embodimentthereof except that 16-value QAM replaces 2^(2m)-value QAM.

According to the third embodiment of this invention, a modulator (aquadrature baseband modulator) in a transmitter includes a 16-value QAMmodulator instead of the 2^(2m)-value QAM modulator 12F (see FIG. 8). Inaddition, a quasi synchronous detector in a receiver includes a 16-valueQAM demodulator instead of the 2^(2m)-value QAM demodulator 29D (seeFIG. 9).

FIG. 12 shows an arrangement of signal points in an I-Q plane which areprovided by the 16-value QAM. In FIG. 12, the signal points are denotedby the reference numeral “601”. The signal points are assigned todifferent logic values respectively. The positions (I_(16QAM),Q_(16QAM)) of the signal points are given by the following equations.I _(16QAM) =r(2¹ a1+2⁰ a2)  (8)Q _(16QAM) =r(2¹ b1+2⁰ b2)  (9)where (a1, b1) and (a2, b2) are binary code words of “1” and “−1”, and“r” denotes a predetermined constant. With reference to FIG. 12,specified ones of the signal points correspond to the maximum amplitudewhich is given as follows.(2¹+2⁰)√{square root over (2)}r  (10)In addition, the distances between the neighboring signal points areequal to a same value given by “2r”.

With reference to FIG. 13, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator in the transmitter (seeFIG. 1), or the RF signal outputted from the RF portion in thetransmitter is composed of a stream of frames each having N successivesymbols. Here, N denotes a predetermined natural number. In every frame,the first symbol results from the QPSK modulation, and the second andlater symbols result from the 16-value QAM. The first symbol in everyframe (that is, the QPSK symbol in every frame) is used by the receiveras a pilot symbol for estimating an amplitude distortion amount and afrequency offset amount. It should be noted that every pilot symbol alsocarries a part of the main information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the GPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to twice the inter-signal-point distance “2r” inthe 16-value QAM. In this case, it is preferable that the quasisynchronous detector in the receiver detects the I-Q-plane amplitude ofthe output I and Q signals of the RF portion when the output I and Qsignals of the RF portion 22 represent a pilot symbol, and that thedetected I-Q-plane amplitude is used as an 1-9-plane amplitude thresholdvalue for the 16-value QAM demodulation.

Fourth Embodiment

A fourth embodiment of this invention is similar to the first embodimentthereof except for design changes indicated hereinafter.

As shown in FIG. 14, a modulator (a quadrature baseband modulator) in atransmitter in the fourth embodiment of this invention includes a QPSKmodulator 12G instead of the QPSK modulator 12B (see FIG. 2).

FIG. 15 shows an arrangement of signal points in an I-Q plane which areprovided by QPSK modulation implemented by the QPSK modulator 12G. InFIG. 15, the signal points are denoted by the reference numeral “801”.The signal points are assigned to different logic values respectively.The positions (I_(QPSKR), Q_(QPSKR)) of the signal points are given bythe following equations.

$\begin{matrix}{I_{QPSKR} = {{I_{QPSK}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} - {Q_{QPSK}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (11) \\{Q_{QPSKR} = {{I_{QPSK}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} + {Q_{QPSK}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (12)\end{matrix}$where “n” denotes an integer, and (I_(QPSK), Q_(QPSK)) are given by theequations (3) and (4). With reference to FIG. 15, all the signal pointscorrespond to a same amplitude given by the constant “p”. In addition,all the distances between the neighboring signal points are equal to asame value given by √{square root over (2p)}. Furthermore, the signalpoints are spaced at equal angular intervals. Accordingly, a QPSKmodulation-resultant signal is suited for detecting an amplitudedistortion and a frequency offset. As shown in FIG. 16, a quasisynchronous detector in a receiver in the fourth embodiment of thisinvention includes a QPSK demodulator 29E instead of the QPSKdemodulator 29B (see FIG. 4).

The QPSK demodulator 29E implements demodulation inverse with respect tothe modulation by the QPSK modulator 12G. A pair of the I signal and theQ signal outputted from the quadrature baseband modulator 12 in thetransmitter 10 (see FIG. 1), or the RF signal outputted from the RFportion 15 in the transmitter 10 is composed of a stream of frames eachhaving N successive symbols. Here, N denotes a predetermined naturalnumber. In every frame, the first symbol results from the QPSKmodulation, and the second and later symbols result from the 16-valueAPSK modulation. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver 20 (see FIG. 3) as apilot symbol for estimating an amplitude distortion amount and afrequency offset amount. It should be noted that every pilot symbol alsocarries a part of the main information to be transmitted.

In the receiver 20, the calculator 25 separates pilot symbols (firstsymbols in frames) from the output I and Q signals of the RF portion 22in response to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 25 estimates an amplitudedistortion amount from the separated pilot symbols. Similarly, thecalculator 26 separates pilot symbols (first symbols in frames) from theoutput I and Q signals of the RF portion 22 in response to a signal (aframe and symbol sync signal) having a period corresponding to Nsymbols. The calculator 26 estimates a frequency offset amount from theseparated pilot symbols.

Preferably, the maximum amplitude g1 provided by the 16-value APSKmodulation is equal to the amplitude “p” provided by the QPSKmodulation. In this case, the amplitude distortion amount and thefrequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver 20 is designed toimplement the following processes. The quasi synchronous detector 29subjects the output I and Q signals of the RF portion 22 to the QPSKdemodulation and outputs the QPSK-demodulation-resultant digital signalwhen the output I and Q signals of the RF portion 22 represent a pilotsymbol. The quasi synchronous detector 29 subjects the output I and Qsignals of the RF portion 22 to the 16-value APSK demodulation andoutputs the APSK-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 22 represent a normal symbol differentfrom a pilot symbol.

Fifth Embodiment

A fifth embodiment of this invention is similar to the second embodimentthereof except for design changes indicated hereinafter.

As shown in FIG. 17, a modulator (a quadrature baseband modulator) in atransmitter in the fifth embodiment of this invention includes a QPSKmodulator 12G instead of the QPSK modulator 12B (see FIG. 8). The QPSKmodulator 12G implements QPSK modulation providing signal points whichare arranged in an I-Q plane as shown in FIG. 15.

As shown in FIG. 18, a quasi synchronous detector in a receiver in thefifth embodiment of this invention includes a QPSK demodulator 29Einstead of the QPSK demodulator 29B (see FIG. 9). The QPSK demodulator29E implements demodulation inverse with respect to the modulation bythe QPSK modulator 12G.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 2^(2m)-value QAM. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver as a pilot symbol forestimating an amplitude distortion amount and a frequency offset amount.It should be noted that every pilot symbol also carries a part of themain information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 2^(2m)-value QAM, thatis, the value given by the expression (7), is equal to the amplitude “p”provided by the GPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 22 represent a normal symbol differentfrom a pilot symbol.

Sixth Embodiment

A sixth embodiment of this invention is similar to the fifth embodimentthereof except that 16-value QAM replaces 2^(2m)-value QAM.

According to the sixth embodiment of this invention, a modulator (aquadrature baseband modulator) in a transmitter includes a 16-value QAMmodulator instead of the 2^(2m)-value QAM modulator 12F (see FIG. 17).The QAM modulator implements 16-value QAM providing signal points whichare arranged in an I-Q plane as shown in FIG. 12. According to the sixthembodiment of this invention, a quasi synchronous detector in a receiverincludes a 16-value QAM demodulator instead of the 2^(2m)-value QAMdemodulator 29D (see FIG. 18).

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 16-value QAM. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver as a pilot symbol forestimating an amplitude distortion amount and a frequency offset amount.It should be noted that every pilot symbol also carries a part of themain information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to twice the inter-signal-point distance “2r” inthe 16-value QAM. In this case, it is preferable that the quasisynchronous detector in the receiver detects the I-Q-plane amplitude ofthe output I and Q signals of the RF portion when the output I and Qsignals of the RF portion 22 represent a pilot symbol, and that thedetected I-Q-plane amplitude is used as an I-Q-plane amplitude thresholdvalue for the 16-value QAM demodulation.

Seventh Embodiment

A seventh embodiment of this invention is similar to the firstembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 19, a modulator (a quadrature baseband modulator) in atransmitter in the seventh embodiment of this invention includes a2^(2m)-value QAM modulator 12H instead of the 16-value APSK modulator12A (see FIG. 2). Here, “m” denotes a predetermined integer equal to orgreater than “2”.

As shown in FIG. 20, a quasi synchronous detector in a receiver in theseventh embodiment of this invention includes a 2^(2m)-value QAMdemodulator 29F instead of the 16-value APSK demodulator 29A (see FIG.4).

FIG. 21 shows an arrangement of signal points in an I-Q plane which areprovided by 2^(2m)-value QAM executed in the QAM modulator 12H. In FIG.21, the signal points are denoted by the reference numeral “901”. Thesignal points are assigned to different logic values respectively. Thepositions of the signal points in FIG. 21 result from rotation of thesignal points in FIG. 10 through an angle of π/4 radian about theorigin. Specifically, the positions (I_(QAMR), Q_(QAMR)) of the signalpoints in FIG. 21 are given by the following equations.

$\begin{matrix}{I_{QAMR} = {{I_{QAM}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} - {Q_{QAM}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (13) \\{Q_{QAMR} = {{I_{QAM}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} + {Q_{QAM}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (14)\end{matrix}$where “n” denotes an integer, and (I_(QAM), Q_(QAM)) are given by theequations (5) and (6). With reference to FIG. 21, the maximum amplitudewhich corresponds to specified ones of the signal points is equal to thevalue given by the expression (7).

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols.

Here, N denotes a predetermined natural number. In every frame, thefirst symbol results from the QPSK modulation, and the second and latersymbols result from the 2^(2m)-value QAM. The first symbol in everyframe (that is, the QPSK symbol in every frame) is used by the receiveras a pilot symbol for estimating an amplitude distortion amount and afrequency offset amount. It should be noted that every pilot symbol alsocarries a part of the main information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 2^(2m)-value QAM, thatis, the value given by the expression (7), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 22 represent a normal symbol differentfrom a pilot symbol.

Eighth Embodiment

An eighth embodiment of this invention is similar to the seventhembodiment thereof except that 16-value QAM replaces 2^(2m)-value QAM.

According to the eighth embodiment of this invention, a modulator (aquadrature baseband modulator) in a transmitter includes a 16-value QAMmodulator instead of the 2^(2m)-value QAM modulator 12H (see FIG. 19).In addition, a quasi synchronous detector in a receiver includes a16-value QAM demodulator instead of the 2^(2m)-value QAM demodulator 29F(see FIG. 20).

FIG. 22 shows an arrangement of signal points in an I-Q plane which areprovided by 16-value QAM executed in the 16-value QAM modulator. In FIG.22, the signal points are denoted by the reference numeral “1001”. Thesignal points are assigned to different logic values respectively. Thepositions of the signal points in FIG. 22 result from rotation of thesignal points in FIG. 12 through an angle of π/4 radian about theorigin. Specifically, the positions (I_(16QAMR), Q_(16QAMR)) of thesignal points in FIG. 22 are given by the following equations.

$\begin{matrix}{I_{16{QAMR}} = {{I_{16{QAM}}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} - {Q_{16{QAM}}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (15) \\{Q_{16{QAMR}} = {{I_{16{QAM}}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} + {Q_{16{QAM}}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (16)\end{matrix}$where “n” denotes an integer, and (I 16QAM, 916QAM) are given by theequations (8) and (9). With reference to FIG. 22, the maximum amplitudewhich corresponds to specified ones of the signal points is equal to thevalue given by the expression (10). In addition, the distances betweenthe neighboring signal points are equal to a same value given by “2r”.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the GPSK modulation, and the second and later symbols result fromthe 16-value QAM. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver as a pilot symbol forestimating an amplitude distortion amount and a frequency offset amount.It should be noted that every pilot symbol also carries a part of themain information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to “√{square root over (2)}” times theinter-signal-point distance “2r” in the 16-value QAM. In this case, itis preferable that the quasi synchronous detector in the receiverdetects the I-Q-plane amplitude of the output I and Q signals of the RFportion when the output I and Q signals of the RF portion 22 represent apilot symbol, and that the detected I-Q-plane amplitude is used as anI-Q-plane amplitude threshold value for the 16-value QAM demodulation.

Ninth Embodiment

A ninth embodiment of this invention is similar to the seventhembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 23, a modulator (a quadrature baseband modulator) in atransmitter in the ninth embodiment of this invention includes a QPSKmodulator 12G instead of the QPSK modulator 12B (see FIG. 19). The QPSKmodulator 12G implements QPSK modulation providing signal points whichare arranged in an I-Q plane as shown in FIG. 15.

As shown in FIG. 24, a quasi synchronous detector in a receiver in theninth embodiment of this invention includes a QPSK demodulator 29Einstead of the QPSK demodulator 29B (see FIG. 20). The QPSK demodulator29E implements demodulation inverse with respect to the modulation bythe QPSK modulator 12G.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 2^(2m)-value QAM. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver as a pilot symbol forestimating an amplitude distortion amount and a frequency offset amount.It should be noted that every pilot symbol also carries a part of themain information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 2^(2m)-value QAM, thatis, the value given by the expression (7), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 22 represent a normal symbol differentfrom a pilot symbol.

Tenth Embodiment

A tenth embodiment of this invention is similar to the ninth embodimentthereof except that 16-value QAM replaces 2^(2m)-value QAM.

According to the tenth embodiment of this invention, a modulator (aquadrature baseband modulator) in a transmitter includes a 16-value QAMmodulator instead of the 2^(2m)-value QAM modulator 12H (see FIG. 23).The 16-value QAM modulator implements 16-value QAM providing signalpoints which are arranged in an I-Q plane as shown in FIG. 22. Accordingto the tenth embodiment of this invention, a quasi synchronous detectorin a receiver includes a 16-value QAM demodulator instead of the2^(2m)-value QAM demodulator 29F (see FIG. 24). The 16-value QAMdemodulator implements demodulation inverse with respect to themodulation by the 16-value QAM modulator.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 16-value QAM. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver as a pilot symbol forestimating an amplitude distortion amount and a frequency offset amount.It should be noted that every pilot symbol also carries a part of themain information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbols(first symbols in frames) from the output I and Q signals of the RFportion 22 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 25 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 26 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 22 in responseto a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that isthe value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the R portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case a sufficientlylow bit error rate is provided.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to twice the inter-signal-point distance “2r” inthe 16-value QAM. In this case, it is preferable that the quasisynchronous detector in the receiver detects the I-Q-plane amplitude ofthe output I and Q signals of the RF portion when the output I and Qsignals of the RF portion 22 represent a pilot symbol, and that thedetected I-Q-plane amplitude is used as an I-Q-plane amplitude thresholdvalue for the 16-value QAM demodulation.

Eleventh Embodiment

An eleventh embodiment of this invention is similar to the thirdembodiment thereof except for design changes indicated hereinafter.

With reference to FIG. 25, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator in the transmitter (seeFIG. 1), or the RF signal outputted from the RF portion in thetransmitter is composed of a stream of frames each having N successivesymbols. Here, N denotes a predetermined natural number. In every frame,first alternate symbols result from the QPSK modulation, and secondalternate symbols result from the 16-value QAM. The QPSK symbols inevery frame are used by the receiver as pilot symbols for estimating anamplitude distortion amount and a frequency offset amount. It should benoted that every pilot symbol also carries a part of the maininformation to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbolsfrom the output I and Q signals of the RF portion 22 in response to asignal (a 2-symbol sync signal) having a period corresponding to twosymbols. The calculator 25 estimates an amplitude distortion amount fromthe separated pilot symbols. Similarly, the calculator 26 separatespilot symbols from the output I and Q signals of the RF portion 22 inresponse to a signal (a 2-symbol sync signal) having a periodcorresponding to 2 symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

With reference to FIG. 26, in the case where the inter-signal-pointdistance “√{square root over (2p)}” in the QPSK modulation is equal to1.20 times the inter-signal-point distance “2r” in the 16-value QAM, thebit error rate provided in the embodiment of this invention decreasesalong the curve A0 as the carrier-to-noise power ratio C/N increases.FIG. 26 also indicates a comparative example being the relation B0between the bit error rate and the carrier-to-noise power ratio C/Nwhich occurs in a prior-art 8PSK (8 or octonary phase shift keying)system. As shown in FIG. 26, the bit error rate (the curve A0) providedin the embodiment of this invention is better than that in the prior-art8PSK system.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to twice the inter-signal-point distance “2r” inthe 16-value QAM. In this case, it is preferable that the quasisynchronous detector in the receiver detects the I-Q-plane amplitude ofthe output I and Q signals of the RF portion when the output I and Qsignals of the RF portion 22 represent a pilot symbol, and that thedetected I-Q-plane amplitude is used as an I-Q-plane amplitude thresholdvalue for the 16-value QAM demodulation.

Twelfth Embodiment

A twelfth embodiment of this invention is similar to the sixthembodiment thereof except for design changes indicated hereinafter.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, first alternate symbolsresult from the QPSK modulation, and second alternate symbols resultfrom the 16-value QAM. The QPSK symbols in every frame are used by thereceiver as pilot symbols for estimating an amplitude distortion amountand a frequency offset amount. It should be noted that every pilotsymbol also carries a part of the main information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbolsfrom the output I and Q signals of the RF portion 22 in response to asignal (a 2-symbol sync signal) having a period corresponding to twosymbols. The calculator 25 estimates an amplitude distortion amount fromthe separated pilot symbols. Similarly, the calculator 26 separatespilot symbols from the output I and Q signals of the RF portion 22 inresponse to a signal (a 2-symbol sync signal) having a periodcorresponding to 2 symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

With reference to FIG. 27, in the case where the inter-signal-pointdistance “√{square root over (2)}p” in the QPSK modulation is equal to1.20 times the inter-signal-point distance “2r” in the 16-value QAM, thebit error rate provided in the embodiment of this invention decreasesalong the curve A1 as the carrier-to-noise power ratio C/N increases.FIG. 27 also indicates a comparative example being the relation B1between the bit error rate and the carrier-to-noise power ratio C/Nwhich occurs in a prior-art 8PSK (8 or octonary phase shift keying)system. As shown in FIG. 27, the bit error rate (the curve A1) providedin the embodiment of this invention is better than that in the prior-art8PSK system.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to “√{square root over (2p)}” times theinter-signal-point distance “2r” in the 16-value QAM. In this case, itis preferable that the quasi synchronous detector in the receiverdetects the I-Q-plane amplitude of the output I and Q signals of the RFportion when the output I and Q signals of the RF portion 22 represent apilot symbol, and that the detected I-Q-plane amplitude is used as anI-Q-plane amplitude threshold value for the 16-value QAM demodulation.

Thirteenth Embodiment

A thirteenth embodiment of this invention is similar to the eighthembodiment thereof except for design changes indicated hereinafter.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, first alternate symbolsresult from the QPSK modulation, and second alternate symbols resultfrom the 16-value QAM. The QPSK symbols in every frame are used by thereceiver as pilot symbols for estimating an amplitude distortion amountand a frequency offset amount. It should be noted that every pilotsymbol also carries a part of the main information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbolsfrom the output I and Q signals of the RF portion 22 in response to asignal (a 2-symbol sync signal) having a period corresponding to twosymbols. The calculator 25 estimates an amplitude distortion amount fromthe separated pilot symbols. Similarly, the calculator 26 separatespilot symbols from the output I and Q signals of the RF portion 22 inresponse to a signal (a 2-symbol sync signal) having a periodcorresponding to 2 symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output Iand Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

With reference to FIG. 28, in the case where the inter-signal-pointdistance “√{square root over (2p)}” in the QPSK modulation is equal to1.20 times the inter-signal-point distance “2r” in the 16-value QAM, thebit error rate provided in the embodiment of this invention decreasesalong the curve A2 as the carrier-to-noise power ratio C/N increases.FIG. 28 also indicates a comparative example being the relation B2between the bit error rate and the carrier-to-noise power ratio C/Nwhich occurs in a prior-art 8PSK (8 or octonary phase shift keying)system. As shown in FIG. 28, the bit error rate (the curve A2) providedin the embodiment of this invention is better than that in the prior-art8PSK system.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to “√{square root over (2)}” times theinter-signal-point distance “2r” in the 16-value QAM. In this case, itis preferable that the quasi synchronous detector in the receiverdetects the I-Q-plane amplitude of the output I and Q signals of the RFportion when the output I and Q signals of the RF portion 22 represent apilot symbol, and that the detected I-Q-plane amplitude is used as anI-Q-plane amplitude threshold value for the 16-value QAM demodulation.

Fourteenth Embodiment

A fourteenth embodiment of this invention is similar to the tenthembodiment thereof except for design changes indicated hereinafter.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 1), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, first alternate symbolsresult from the QPSK modulation, and second alternate symbols resultfrom the 16-value QAM. The QPSK symbols in every frame are used by thereceiver as pilot symbols for estimating an amplitude distortion amountand a frequency offset amount. It should be noted that every pilotsymbol also carries a part of the main information to be transmitted.

In the receiver (see FIG. 3), the calculator 25 separates pilot symbolsfrom the output I and Q signals of the RF portion 22 in response to asignal (a 2-symbol sync signal) having a period corresponding to twosymbols. The calculator 25 estimates an amplitude distortion amount fromthe separated pilot symbols. Similarly, the calculator 26 separatespilot symbols from the output I and Q signals of the RF portion 22 inresponse to a signal (a 2-symbol sync signal) having a periodcorresponding to 2 symbols. The calculator 26 estimates a frequencyoffset amount from the separated pilot symbols.

Preferably, the maximum amplitude provided by the 16-value QAM, that is,the value given by the expression (10), is equal to the amplitude “p”provided by the QPSK modulation. In this case, the amplitude distortionamount and the frequency offset amount can be accurately estimated.

The quasi synchronous detector 29 in the receiver (see FIG. 3) isdesigned to implement the following processes. The quasi synchronousdetector 29 subjects the output I and Q signals of the RF portion 22 toQPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 22 represent apilot symbol. The quasi synchronous detector 29 subjects the output I,and Q signals of the RF portion 22 to 16-value QAM demodulation and theQAM-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 22 represent a normal symbol different from apilot symbol.

In general, the inter-signal-point distance “√{square root over (2p”)}in the QPSK modulation is equal to a given value times theinter-signal-point distance “2r” in the 16-value QAM. Preferably, thegiven value is in the range of 0.90 to 1.50. In this case, asufficiently low bit error rate is provided.

With reference to FIG. 29, in the case where the inter-signal-pointdistance “√{square root over (2p)}” in the QPSK modulation is equal to1.20 times the inter-signal-point distance “2r” in the 16-value QAM, thebit error rate provided in the embodiment of this invention decreasesalong the curve A3 as the carrier-to-noise power ratio C/N increases.FIG. 29 also indicates a comparative example being the relation B3between the bit error rate and the carrier-to-noise power ratio C/Nwhich occurs in a prior-art 8PSK (8 or octonary phase shift keying)system. As shown in FIG. 29, the bit error rate (the curve A3) providedin the embodiment of this invention is better than that in the prior-art8PSK system.

The inter-signal-point distance “√{square root over (2p”)} in the QPSKmodulation may be equal to twice the inter-signal-point distance “2r” inthe 16-value QAM. In this case, it is preferable that the quasisynchronous detector in the receiver detects the I-Q-plane amplitude ofthe output I and Q signals of the RF portion when the output I and Qsignals of the RF portion 22 represent a pilot symbol, and that thedetected I-Q-plane amplitude is used as an I-Q-plane amplitude thresholdvalue for the 16-value QAM demodulation.

Fifteenth Embodiment

FIG. 30 shows a transmitter 110 in a radio communication systemaccording to a fifteenth embodiment of this invention. With reference toFIG. 30, the transmitter 110 includes a modulator (a quadrature basebandmodulator) 112 and an RF (radio frequency) portion 115.

A digital signal to be transmitted (that is, an input digital signal ormain information to be transmitted) is fed to the quadrature basebandmodulator 112. The device 112 subjects the input digital signal toquadrature baseband modulation, thereby converting the input digitalsignal into a pair of modulation-resultant baseband signals, that is, abaseband I (in-phase) signal and a baseband Q (quadrature) signal. Thequadrature baseband modulator 112 outputs the baseband I signal and thebaseband Q signal to the RF portion 115.

The RF portion 115 converts the baseband I signal and the baseband Qsignal into an RF signal through frequency conversion.

The RF portion 115 feeds the RF signal to an antenna 117. The RF signalis radiated by the antenna 117.

As shown in FIG. 31, the quadrature baseband modulator 112 includes a8PSK (8 or octonary phase shift keying) modulator 112A, a BPSK (binaryphase shift keying) modulator 112B, a reference signal generator 112C,and switches 112D and 112E.

The 8PSK modulator 112A and the BPSK modulator 112B receives the inputdigital signal. The device 112A subjects the input digital signal to8PSK (8PSK modulation), thereby converting the input digital signal intoa pair of a baseband I signal and a baseband Q signal. The 8PSKmodulator 112A outputs the baseband I signal to the switch 112D. The8PSK modulator 112A outputs the baseband Q signal to the switch 112E.The device 112B subjects the input digital signal to BPSK (BPSKmodulation), thereby converting the input digital signal into a pair ofa baseband I signal and a baseband Q signal. The BPSK modulator 112Boutputs the baseband I signal to the switch 112D. The BPSK modulator112B outputs the baseband Q signal to the switch 112E. The referencesignal generator 112C outputs a reference baseband I signal to theswitch 112D. The reference signal generator 112C outputs a referencebaseband Q signal to the switch 112E. The output I and Q signals fromthe reference signal generator 112C are used in acquiringsynchronization between the transmitter 110 and a receiver during aninitial stage of signal transmission. The switch 112D selects one of theoutput I signal from the 8PSK modulator 112A, the output I signal fromthe BPSK modulator 112B, and the output I signal from the referencesignal generator 112C, and transmits the selected signal to the RFportion 115. The switch 112E selects one of the output Q signal from the8PSK modulator 112A, the output Q signal from the BPSK modulator 112B,and the output Q signal from the reference signal generator 112C, andtransmits the selected Q signal to the RF portion 115.

During an initial stage of signal transmission, the switch 112D selectsthe output I signal from the reference signal generator 112C while theswitch 112D selects the output Q signal from the reference signalgenerator 112C. During an interval of time which follows the initialstage, the switch 112D alternately selects the output I signal from the8PSK modulator 112A and the output I signal from the BPSK modulator 112Bat a predetermined period, and transmits the selected I signal to the RFportion 115. During the time interval following the initial stage, theswitch 112E alternately selects the output Q signal from the 8PSKmodulator 112A and the output Q signal from the BPSK modulator 112B atthe predetermined period, and transmits the selected Q signal to the RFportion 115.

Accordingly, with respect to the input digital signal, the quadraturebaseband modulator 112 alternately implements the 8PSK modulation andthe BPSK modulation at the predetermined period.

In the quadrature baseband modulator 112, the output I and Q signalsfrom the BPSK modulator 112B are fed to the 8PSK modulator 112A. The8PSK modulation implemented by the device 112A depends on the output Iand Q signals from the BPSK modulator 112B.

FIG. 32 shows a receiver 120 in the radio communication system accordingto the fifteenth embodiment of this invention. With reference to FIG.32, the receiver 120 includes an RF portion 122, calculators 125 and126, and a quasi synchronous detector 129.

An RF signal caught by an antenna 121 is applied to the RF portion 122.The RF portion 122 subjects the applied RF signal to frequencyconversion, thereby converting the applied RF signal into a pair of abaseband I signal and a baseband Q signal. The RF portion 122 outputsthe baseband I signal and the baseband Q signal to the calculators 125and 126, and the quasi synchronous detector 129.

The calculator 125 estimates an amplitude distortion amount from thebaseband I signal and the baseband Q signal. The calculator 125 informsthe quasi synchronous detector 129 of the estimated amplitude distortionamount. The calculator 126 estimates a frequency offset amount from thebaseband I signal and the baseband Q signal. The calculator 126 informsthe quasi synchronous detector 129 of the estimated frequency offsetamount.

The device 129 subjects the baseband I signal and the baseband Q signalto quasi synchronous detection responsive to the estimated amplitudedistortion amount and the estimated frequency offset amount, therebydemodulating the baseband I signal and the baseband Q signal into anoriginal digital signal. Thus, the quasi synchronous detector 129recovers the original digital signal from the baseband I signal and thebaseband Q signal. The quasi synchronous detector 129 outputs therecovered original digital signal.

As shown in FIG. 33, the quasi synchronous detector 129 includes an 8PSKdemodulator 129A, a BPSK demodulator 129B, and a switch 129C.

The 8PSK demodulator 129A and the BPSK demodulator 129B receive theoutput I and Q signals from the RF portion 122. In addition, the 8PSKdemodulator 129A and the BPSK demodulator 129B are informed of theestimated amplitude distortion amount and the estimated frequency offsetamount by the calculators 125 and 126.

The device 129A subjects the baseband I signal and the baseband Q signalto 8PSK demodulation responsive to the estimated amplitude distortionamount and the estimated frequency offset amount, thereby demodulatingthe baseband I signal and the baseband Q signal into an original digitalsignal. Thus, the 8PSK demodulator 129A recovers the original digitalsignal from the baseband I signal and the baseband Q signal. The 8PSKdemodulator 129A outputs the recovered original digital signal to theswitch 129C.

The device 129B subjects the baseband I signal and the baseband Q signalto BPSK demodulation responsive to the estimated amplitude distortionamount and the estimated frequency offset amount, thereby demodulatingthe baseband I signal and the baseband Q signal into an original digitalsignal. Thus, the BPSK demodulator 129B recovers the original digitalsignal from the baseband I signal and the baseband Q signal. The BPSKdemodulator 129B outputs the recovered original digital signal to theswitch 129C.

The switch 129C alternately selects the output digital signal from the8PSK demodulator 129A and the output digital signal from the BPSKdemodulator 129B in response to a timing signal (a frame and symbol syncsignal), and transmits the selected digital signal to a later stage.When the baseband I and Q signals outputted from the RF portion 122 tothe quasi synchronous detector 129 correspond to a result of the 8PSKmodulation, the switch 129C selects the output digital signal from the8PSK demodulator 129A. When the baseband I and Q signals outputted fromthe RF portion 122 to the quasi synchronous detector 129 correspond to aresult of the BPSK modulation, the switch 129C selects the outputdigital signal from the BPSK demodulator 129B.

For example, the 8PSK demodulator 129A includes an amplitude correctioncircuit and a frequency correction circuit. The amplitude correctioncircuit compensates for an amplitude distortion of the baseband I signaland the baseband Q signal in response to the estimated amplitudedistortion, thereby generating a first compensation-resultant baseband Isignal and a first compensation-resultant baseband Q signal. Thefrequency correction circuit compensates for a frequency offset of thefirst compensation-resultant baseband I signal and the firstcompensation-resultant baseband Q signal in response to the estimatedfrequency offset amount, thereby generating a secondcompensation-resultant baseband I signal and a secondcompensation-resultant baseband Q signal. In the 8PSK demodulator 129A,the second compensation-resultant baseband I signal and the secondcompensation-resultant baseband Q signal are subjected to the 8PSKdemodulation, being converted into the original digital signal.

For example, the BPSK demodulator 129B includes an amplitude correctioncircuit and a frequency correction circuit. The amplitude correctioncircuit compensates for an amplitude distortion of the baseband I signaland the baseband Q signal in response to the estimated amplitudedistortion, thereby generating a first compensation-resultant baseband Isignal and a first compensation-resultant baseband Q signal. Thefrequency correction circuit compensates for a frequency offset of thefirst compensation-resultant baseband I signal and the firstcompensation-resultant baseband Q signal in response to the estimatedfrequency offset amount, thereby generating a secondcompensation-resultant baseband I signal and a secondcompensation-resultant baseband Q signal. In the BPSK demodulator 129B,the second compensation-resultant baseband I signal and the secondcompensation-resultant baseband Q signal are subjected to the BPSKdemodulation, being converted into the original digital signal.

FIG. 34 shows an arrangement of 8 signal points in an I-Q plane whichare provided by the 8PSK modulation. In FIG. 34, the 8 signal points aredenoted by the reference numeral “101A”. The 8 signal points areassigned to 8 different levels (8 different logic states) respectively.The positions (I_(8PSK), Q_(8PSK)) of the 8 signal points are given bythe following equations.

$\begin{matrix}{I_{8{PSK}} = {p \cdot {\cos\left( \frac{k\;\pi}{4} \right)}}} & (17) \\{Q_{8{PSK}} = {p \cdot {\sin\left( \frac{k\;\pi}{4} \right)}}} & (18)\end{matrix}$where “k” denotes a variable integer, and “p” denotes a predeterminedconstant.

FIG. 35 shows an arrangement of two signal points in an I-Q plane whichare provided by the BPSK modulation. In FIG. 35, the signal points aredenoted by the reference numeral “201A”. The positions (I_(BPSK),Q_(BPSK)) of the signal points are given by the following equations.I _(BPSK) =q·cos(kπ)  (19)Q _(BPSK) =q·sin(kπ)  (20)where “k” denotes a variable integer, and “q” denotes a predeterminedconstant. With reference to FIG. 35, the signal points are on the Iaxis, and correspond to a same amplitude given by the constant “q”. Inaddition, the signal points are spaced at an angle of π radian.Accordingly, a BPSK modulation-resultant signal is suited for detectingan amplitude distortion and a frequency offset.

With reference to FIG. 36, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator 112 in the transmitter110, or the RF signal outputted from the RF portion 115 in thetransmitter 110 is composed of a stream of frames each having Nsuccessive symbols. Here, N denotes a predetermined natural number. Inevery frame, the first symbol results from the BPSK modulation, and thesecond and later symbols result from the 8PSK modulation. The firstsymbol in every frame (that is, the BPSK symbol in every frame) is usedby the receiver 120 as a pilot symbol for estimating an amplitudedistortion amount and a frequency offset amount. It should be noted thatevery pilot symbol also carries a part of the main information to betransmitted.

In the receiver 120, the calculator 125 separates pilot symbols (firstsymbols in frames) from the output I and Q signals of the RF portion 122in response to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 125 estimates an amplitudedistortion amount from the separated pilot symbols. Similarly, thecalculator 126 separates pilot symbols (first symbols in frames) fromthe output I and Q signals of the RF portion 122 in response to a signal(a frame and symbol sync signal) having a period corresponding to Nsymbols. The calculator 126 estimates a frequency offset amount from theseparated pilot symbols.

The quasi synchronous detector 129 in the receiver 120 is designed toimplement the following processes. The quasi synchronous detector 129subjects the output I and Q signals of the RF portion 122 to the BPSKdemodulation and outputs the BPSK-demodulation-resultant digital signalwhen the output I and Q signals of the RF portion 122 represent a pilotsymbol. The quasi synchronous detector 129 subjects the output I and Qsignals of the RF portion 122 to the 8PSK demodulation and outputs the8PSK-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 122 represent a normal symbol different from apilot symbol.

The BPSK modulator 112B in the quadrature baseband modulator 112 of thetransmitter 110 is designed to implement processes indicated below. Thephase of an i-th BPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th BPSK symbol in the I-Q plane is denoted by“φ_(i+1)”. The BPSK modulator 112B determines the phase “θ_(i+1)” of the(i+1)-th BPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the followingequation.θ_(i+1)=φ_(i)+1−φ_(i) (mod. 2π)  (21)The BPSK modulator 112B implements BPSK modulation providing two signalpoints which are respectively on the positive side and the negative sideof the x axis in the x-y plane as shown in FIG. 37. The BPSK modulator112B assigns a bit of “0” and a bit of “1” in the input digital signalto the positive signal point and the negative signal point,respectively. Accordingly, a bit of “0” corresponds to the absence of aphase change of π radian between two successively symbols while a bit of“1” corresponds to the presence of a phase change of π radian betweentwo successively symbols as in differential phase shift keying (DPSK).The BPSK modulator 112B outputs a pair of modulation-resultant I and Qsignals to the switches 112D and 112E. The BPSK modulator 112B includesa latch or a register for sampling and holding a pair ofmodulation-resultant I and Q signals which are selected by the switches112D and 112E. The modulation-resultant I and Q signals held by thelatch or the register are periodically updated. The BPSK modulator 112Boutputs a pair of held modulation-resultant I and Q signals to the 8PSKmodulator 112A.

As previously indicated, the 8PSK modulation implemented by the 8PSKmodulator 112A provides 8 different signal points to which 8 differentlogic states are assigned respectively. For symbols following a BPSKsymbol in every frame, the 8PSK modulator 112A determines the assignmentof the logic states to the signal points on the basis of the signalpoint used by the BPSK symbol. The signal point used by the BPSK symbolis represented by a pair of BPSK-modulation-resultant I and Q signalsfed from the BPSK modulator 112B. In the case where a signal point 501on the positive side of the I axis is used by a BPSK symbol, the 8PSKmodulator 112A assigns 3-bit sets of “000”, “001”, “010”, “011”, “100”,“101”, “110”, and “111” in the input digital signal to eight signalpoints 502 for following symbols as shown in FIG. 38. In the case wherea signal point 501 on the negative side of the I axis is used by a BPSKsymbol, the 8PSK modulator 112A assigns 3-bit sets of “000”, “001”,“010”, “011”, “100”, “101”, “110”, and “111” in the input digital signalto eight signal points 502 for following symbols as shown in FIG. 39.

Sixteenth Embodiment

A sixteenth embodiment of this invention is similar to the fifteenthembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 40, a modulator (a quadrature baseband modulator) in atransmitter in the sixteenth embodiment of this invention includes a2^(2m)-value QAM (quadrature amplitude modulation) modulator 112Finstead of the 8PSK modulator 112A (see FIG. 31). Here, “m” denotes apredetermined integer equal to or greater than “2”.

As shown in FIG. 41, a quasi synchronous detector in a receiver in thesixteenth embodiment of this invention includes a 2^(2m)-value QAMdemodulator 129D instead of the 8PSK demodulator 129A (see FIG. 33). The2^(2m)-value QAM demodulator 129D implements demodulation inverse withrespect to the modulation by the QAM modulator 112F.

FIG. 42 shows an arrangement of signal points in an I-Q plane which areprovided by 2^(2m)-value QAM executed in the QAM modulator 112F. In FIG.42, the signal points are denoted by the reference numeral “601A”. Thesignal points are assigned to different values (different logic states)respectively. The positions (I_(QAM), Q_(QAM)) of the signal points aregiven by the following equations.I _(QAM) =r(2^(m-1) a1+2^(m-2) a2+••• +2⁰ am)  (22)Q _(QAM) =r(2^(m-1) b1+2^(m-2) b2+••• +2⁰ bm)  (23)where “m” denotes a predetermined integer equal to or greater than “2”;(a1, b1), (a2, b2), . . . , (am, bm) are binary code words of “1” and“−1”; and “r” denotes a predetermined constant.

An example of the 2^(2m)-value QAM executed in the QAM modulator 112F is16-value QAM. FIG. 43 shows an arrangement of signal points in an I-Qplane which are provided by the 16-value QAM. In FIG. 43, the signalpoints are denoted by the reference numeral “701”. The signal points areassigned to different values (different logic states) respectively. Thepositions (I_(16QAM), Q_(16QAM)) of the signal points are given by thefollowing equations.I _(16QAM) =s(2¹ a1+2⁰ a2)  (24)Q _(16QAM) =s(2¹ b1+2⁰ b2)  (25)where (a1, b1) and (a2, b2) are binary code words of “1” and “−1”, and“s” denotes a predetermined constant.

With reference to FIG. 44, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator in the transmitter (seeFIG. 30), or the RF signal outputted from the RF portion in thetransmitter is composed of a stream of frames each having N successivesymbols. Here, N denotes a predetermined natural number. In every frame,the first symbol results from the BPSK modulation, and the second andlater symbols result from the 16-value QAM. The first symbol in everyframe (that is, the BPSK symbol in every frame) is used by the receiveras a pilot symbol for estimating an amplitude distortion amount and afrequency offset amount. It should be noted that every pilot symbol alsocarries a part of the main information to be transmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to BPSK demodulation and outputs the BPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 16-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 122 represent a normal symbol differentfrom a pilot symbol.

The 16-value QAM implemented by the 16-value QAM modulator 112A provides16 different signal points to which 16 different logic states areassigned respectively. For symbols following a BPSK symbol in everyframe, the 16-value QAM modulator 112A determines the assignment of thelogic stages to the signal points on the basis of the signal point usedby the BPSK symbol. The signal point used by the BPSK symbol isrepresented by a pair of BPSK-modulation-resultant I and Q signals fedfrom the BPSK modulator 112B. In the case where a signal point 901A onthe positive side of the I axis is used by a BPSK symbol, the 16-valueQAM modulator 112A assigns 4-bit sets of “0000”, “0001”, “0010”, . . . ,“1110”, and “1111” in the input digital signal to 16 signal points 902for following symbols as shown in FIG. 45. In the case where a signalpoint 901A on the negative side of the I axis is used by a BPSK symbol,the 16-value QAM modulator 112A assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal to 16signal points 902 for following symbols as shown in FIG. 46.

Seventeenth Embodiment

A seventeenth embodiment of this invention is similar to the fifteenthembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 47, a modulator (a quadrature baseband modulator) in atransmitter in the seventeenth embodiment of this invention includes a2^(2m)-value QAM (quadrature amplitude modulation) modulator 112Ginstead of the 8PSK modulator 112A (see FIG. 31). Here, “m” denotes apredetermined integer equal to or greater than “2”.

As shown in FIG. 48, a quasi synchronous detector in a receiver in theseventeenth embodiment of this invention includes a 2^(2m)-value QAMdemodulator 129E instead of the 8PSK demodulator 129A (see FIG. 33). The2^(2m)-value QAM demodulator 129E implements demodulation inverse withrespect to the modulation by the QAM modulator 112G.

FIG. 49 shows an arrangement of signal points in an I-Q plane which areprovided by 2^(2m)-value QAM executed in the QAM modulator 112G. In FIG.49, the signal points are denoted by the reference numeral “1001A”. Thesignal points are assigned to different logic values respectively. Thepositions of the signal points in FIG. 49 result from rotation of thesignal points in FIG. 42 through an angle of π/4 radian about theorigin. Specifically, the positions (I_(QAMR), Q_(QAMR)) of the signalpoints in FIG. 49 are given by the following equations.

$\begin{matrix}{I_{QAMR} = {{I_{QAM}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} - {Q_{QAM}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (26) \\{Q_{QAMR} = {{I_{QAM}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} + {Q_{QAM}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (27)\end{matrix}$where “n” denotes an integer, and (I_(QAM), Q_(QAM)) are given by theequations (22) and (23).

An example of the 2^(2m)-value QAM executed in the QAM modulator 112G is16-value QAM. FIG. 50 shows an arrangement of signal points in an I-Qplane which are provided by the 16-value QAM. In FIG. 50, the signalpoints are denoted by the reference numeral “1101”. The signal pointsare assigned to different logic states (different values) respectively.The positions of the signal points in FIG. 50 result from rotation ofthe signal points in FIG. 43 through an angle of π/4 radian about theorigin. Specifically, the positions (I_(16QAMR), Q_(16QAMR)) of thesignal points in FIG. 50 are given by the following equations.

$\begin{matrix}{I_{16{QAMR}} = {{I_{16{QAM}}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} - {Q_{16{QAM}}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (28) \\{Q_{16{QAMR}} = {{I_{16{QAM}}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} + {Q_{16{QAM}}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (29)\end{matrix}$where “n” denotes an integer, and (I_(16QAM), Q_(16QAM)) are given bythe equations (24) and (25).

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 30), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the BPSK modulation, and the second and later symbols result fromthe 16-value QAM. The first symbol in every frame (that is, the BPSKsymbol in every frame) is used by the receiver as a pilot symbol forestimating an amplitude distortion amount and a frequency offset amount.It should be noted that every pilot symbol also carries a part of themain information to be transmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to BPSK demodulation and outputs the BPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 16-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 122 represent a normal symbol differentfrom a pilot symbol.

The 16-value QAM implemented by the 16-value QAM modulator 112G provides16 different signal points to which 16 different logic states areassigned respectively. For symbols following a BPSK symbol in everyframe, the 16-value QAM modulator 112G determines the assignment of thelogic states to the signal points on the basis of the signal point usedby the BPSK symbol. The signal point used by the BPSK symbol isrepresented by a pair of BPSK-modulation-resultant I and Q signals fedfrom the BPSK modulator 112B. In the case where a signal point 1201 onthe positive side of the I axis is used by a BPSK symbol, the 16-valueQAM modulator 112G assigns 4-bit sets of “0000”, “0001”, “0010”, . . . ,“1110”, and “1111” in the input digital signal to 16 signal points 1202for following symbols as shown in FIG. 51. In the case where a signalpoint 1201 on the negative side of the I axis is used by a BPSK symbol,the 16-value QAM modulator 112G assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal to 16signal points 1202 for following symbols as shown in FIG. 52.

Eighteenth Embodiment

An eighteenth embodiment of this invention is similar to the fifteenthembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 53, a modulator (a quadrature baseband modulator) in atransmitter in the eighteenth embodiment of this invention includes aQPSK (quadrature phase shift keying) modulator 112H instead of the BPSKmodulator 112B (see FIG. 31).

As shown in FIG. 54, a quasi synchronous detector in a receiver in theeighteenth embodiment of this invention includes a QPSK demodulator 129Finstead of the BPSK demodulator 129B (see FIG. 33). The QPSK demodulator129F implements demodulation inverse with respect to the modulation bythe QPSK modulator 112H.

FIG. 55 shows an arrangement of signal points in an I-Q plane which areprovided by the QPSK modulation executed in the QPSK modulator 112H. InFIG. 55, the signal points are denoted by the reference numeral “1301”.The positions (I_(QPSK), Q_(QPSK)) of the signal points are given by thefollowing equations.

$\begin{matrix}{I_{QPSK} = {u\left\{ {{{\cos\left( \frac{\pi}{4} \right)}{\cos\left( \frac{k\;\pi}{2} \right)}} - {{\sin\left( \frac{\pi}{4} \right)}{\sin\left( \frac{k\;\pi}{2} \right)}}} \right\}}} & (30) \\{Q_{QPSK} = {u\left\{ {{{\cos\left( \frac{\pi}{4} \right)}{\sin\left( \frac{k\;\pi}{2} \right)}} + {{\sin\left( \frac{\pi}{4} \right)}{\cos\left( \frac{k\;\pi}{2} \right)}}} \right\}}} & (31)\end{matrix}$where “k” denotes a variable integer, and “u” denotes a predeterminedconstant. With reference to FIG. 55, all the signal points correspond toa same amplitude given by the constant “u”. In addition, all thedistances between the neighboring signal points are equal to a samevalue given by √{square root over (2u)}. Furthermore, the signal pointsare spaced at equal angular intervals. Accordingly, a QPSKmodulation-resultant signal is suited for detecting an amplitudedistortion and a frequency offset.

With reference to FIG. 56, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator in the transmitter (seeFIG. 30), or the RF signal outputted from the RF portion in thetransmitter is composed of a stream of frames each having N successivesymbols. Here, N denotes a predetermined natural number. In every frame,the first symbol results from the QPSK modulation, and the second andlater symbols result from the 8PSK modulation. The first symbol in everyframe (that is, the QPSK symbol in every frame) is used by the receiver(see FIG. 32) as a pilot symbol for estimating an amplitude distortionamount and a frequency offset amount. It should be noted that everypilot symbol also carries a part of the main information to betransmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to QPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 8PSK demodulation and outputs the8PSK-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 122 represent a normal symbol different from apilot symbol.

The QPSK modulator 112H in the quadrature baseband modulator 112 of thetransmitter is designed to implement processes indicated below. Thephase of an i-th QPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th QPSK symbol in the I-Q plane is denoted by“φ_(i+1)”. The QPSK modulator 112H determines the phase “θ_(i+1)” of the(i+1)-th QPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the followingequation.φ_(i)+1=φ_(i)+1−φ_(i)(mod. 2π)  (32)The QPSK modulator 112H implements QPSK modulation providing four signalpoints which are respectively on the positive side of the x axis, thenegative side of the x axis, the positive side of the y axis, and thenegative side of the y axis in the x-y plane as shown in FIG. 57. TheQPSK modulator 112H assigns 2-bit sets of “00”, “01”, “10”, and “11” tothe positive-x signal point, the positive-y signal point, the negativelysignal point, and the negative-x signal point, respectively.Accordingly, a 2-bit set of “00” corresponds to the absence of any phasechange between two successive symbols. A 2-bit set of “01” correspondsto the presence of a phase change of π/2 radian between two successivesymbols. A 2-bit set of “11” corresponds to the presence of a phasechange of π radian between two successive symbols. A 2-bit set of “10”corresponds to the presence of a phase change of 3π/2 radian between twosuccessive symbols. The QPSK modulator 112H outputs a pair ofmodulation-resultant I and Q signals to the switches 112D and 112E. TheQPSK modulator 112H includes a latch or a register for sampling andholding a pair of modulation-resultant I and Q signals which areselected by the switches 112D and 112E. The modulation-resultant I and Qsignals held by the latch or the register are periodically updated. TheQPSK modulator 112H outputs a pair of held modulation-resultant I and Qsignals to the 8PSK modulator 112A.

The 8PSK modulation implemented by the 8PSK modulator 112A provides 8different signal points to which 8 different logic states are assignedrespectively. For symbols following a GPSK symbol in every frame, the8PSK modulator 112A determines the assignment of the logic states to thesignal points on the basis of the signal point used by the QPSK symbol.The signal point used by the QPSK symbol is represented by a pair ofQPSK-modulation-resultant I and Q signals fed from the QPSK modulator112H. In the case where a positive-I positive-Q signal point 1601 isused by a QPSK symbol, the 8PSK modulator 112A assigns 3-bit sets of“000”, “001”, “010”, “011”, “100”, “101”, “110”, and “111” in the inputdigital signal to eight signal points 1602 for following symbols asshown in FIG. 58. In the case where a negative-I positives signal point1601 is used by a QPSK symbol, the 8PSK modulator 112A assigns 3-bitsets of “000”, “001”, “010”, “011”, “100”, “101”, “110”, and “111” inthe input digital signal to eight signal points 1602 for followingsymbols as shown in FIG. 59. In the case where a negative-I negative-Qsignal point 1601 is used by a QPSK symbol, the 8PSK modulator 112Aassigns 3-bit sets of “000”, “001”, “010”, “011”, “100”, “101”, “110”,and “111” in the input digital signal to eight signal points 1602 forfollowing symbols as shown in FIG. 60. In the case where a positive-Inegative-Q signal point 1601 is used by a QPSK symbol, the 8PSKmodulator 112A assigns 3-bit sets of “000”, “001”, “010”, “011”, “100”,“101”, “110”, and “111” in the input digital signal to eight signalpoints 1602 for following symbols as shown in FIG. 61.

Nineteenth Embodiment

A nineteenth embodiment of this invention is similar to the sixteenthembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 62, a modulator (a quadrature baseband modulator) in atransmitter in the nineteenth embodiment of this invention includes aQPSK modulator 112H instead of the BPSK modulator 112B (see FIG. 40).

As shown in FIG. 63, a quasi synchronous detector in a receiver in thenineteenth embodiment of this invention includes a QPSK demodulator 129Finstead of the BPSK demodulator 129B (see FIG. 41). The QPSK demodulator129F implements demodulation inverse with respect to the modulation bythe QPSK modulator 112H.

The QPSK modulator 112H implements QPSK modulation providing signalpoints which are arranged in an I-Q plane as shown in FIG. 55. Thepositions (I_(QPSK), Q_(QPSK)) of the signal points are given by theequations (30) and (31).

With reference to FIG. 64, a pair of the I signal and the Q signaloutputted from the quadrature baseband modulator in the transmitter (seeFIG. 30), or the RF signal outputted from the RF portion in thetransmitter is composed of a stream of frames each having N successivesymbols. Here, N denotes a predetermined natural number. In every frame,the first symbol results from the QPSK modulation, and the second andlater symbols result from the 2^(2m)-value QAM, for example, the16-value QAM. The first symbol in every frame (that is, the QPSK symbolin every frame) is used by the receiver (see FIG. 32) as a pilot symbolfor estimating an amplitude distortion amount and a frequency offsetamount. It should be noted that every pilot symbol also carries a partof the main information to be transmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to QPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 122 represent a normal symbol differentfrom a pilot symbol.

The QPSK modulator 112H in the quadrature baseband modulator 112 of thetransmitter is designed to implement processes indicated below. Thephase of an i-th QPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th QPSK symbol in the I-Q plane is denoted by“φ_(i+1)” The QPSK modulator 112H determines the phase “θ_(i+1)” of the(i+1)-th QPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the equation (32).The QPSK modulator 112H implements QPSK modulation providing four signalpoints which are respectively on the positive side of the x axis, thenegative side of the x axis, the positive side of the y axis, and thenegative side of the y axis in the x-y plane as shown in FIG. 57. TheQPSK modulator 112H assigns 2-bit sets of “00”, “01”, “10”, and “11” tothe positive-x signal point, the positively signal point, the negativelysignal point, and the negative-x signal point, respectively. The QPSKmodulator 112H outputs a pair of modulation-resultant I and Q signals tothe switches 112D and 112E. The QPSK modulator 112H includes a latch ora register for sampling and holding a pair of modulation-resultant I andQ signals which are selected by the switches 112D and 112E. Themodulation-resultant I and Q signals held by the latch or the registerare periodically updated. The QPSK modulator 112H outputs a pair of heldmodulation-resultant I and Q signals to the 2^(2m)-value QAM modulator112F.

An example of the modulation implemented by the 2^(2m)-value QAMmodulator 112F is the 16-value QAM. The 16-value QAM by the 2^(2m)-valueQAM modulator 112F provides 16 different signal points to which 16different logic states are assigned respectively. For symbols followinga QPSK symbol in every frame, the 16-value QAM modulator 112F determinesthe assignment, of the logic states to the signal points on the basis ofthe signal point used by the QPSK symbol. The signal point used by theQPSK symbol is represented by a pair of QPSK-modulation-resultant I andQ signals fed from the QPSK modulator 112H. In the case where apositive-I positive-Q signal point 1801 is used by a QPSK symbol, the16-value QAM modulator 112F assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal tosixteen signal points 1802 for following symbols as shown in FIG. 65. Inthe case where a negative-I positive-Q signal point 1801 is used by aQPSK symbol, the 16-value QAM modulator 112F assigns 4-bit sets of“0000”, “00011”, “0010”, . . . , “1110”, and “1111” in the input digitalsignal to sixteen signal points 1802 for following symbols as shown inFIG. 66. In the case where a negative-I negative-Q signal point 1801 isused by a QPSK symbol, the 16-value QAM modulator 112F assigns 4-bitsets of “0000”, “0001”, “0010”, . . . , “1110”, and “1111” in the inputdigital signal to sixteen signal points 1802 for following symbols asshown in FIG. 67. In the case where a positive-I negative-Q signal point1801 is used by a QPSK symbol, the 16-value QAM modulator 112F assigns4-bit sets of “0000”, “0001”, “0010”, . . . , “1110”, and “1111” in theinput digital signal to sixteen signal points 1802 for following symbolsas shown in FIG. 68.

Twentieth Embodiment

A twentieth embodiment of this invention is similar to the fifteenthembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 69, a modulator (a quadrature baseband modulator) in atransmitter in the twentieth embodiment of this invention includes aQPSK (quadrature phase shift keying) modulator 112J instead of the BPSKmodulator 112B (see FIG. 31).

As shown in FIG. 70, a quasi synchronous detector in a receiver in thetwentieth embodiment of this invention includes a QPSK demodulator 129Ginstead of the BPSK demodulator 129B (see FIG. 33). The QPSK demodulator129G implements demodulation inverse with respect to the modulation bythe QPSK modulator 112J.

FIG. 71 shows an arrangement of signal points in an I-Q plane which areprovided by QPSK modulation implemented by the QPSK modulator 112J. InFIG. 71, the signal points are denoted by the reference numeral “1901”.The positions (I_(QPSKR), Q_(QPSKR)) of the signal points are given bythe following equations.

$\begin{matrix}{I_{QPSKR} = {{I_{QPSK}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} - {Q_{QPSK}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (33) \\{Q_{QPSKR} = {{I_{QPSK}\left\{ {\sin\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}} + {Q_{QPSK}\left\{ {\cos\left( {\frac{\pi}{4} + \frac{n\;\pi}{2}} \right)} \right\}}}} & (34)\end{matrix}$where “n” denotes an integer, and (I_(QPSK), Q_(QPSK)) are given by theequations (30) and (31). With reference to FIG. 71, all the signalpoints correspond to a same amplitude. In addition, all the distancesbetween the neighboring signal points are equal to a same value.Furthermore, the signal points are spaced at equal angular intervals.Accordingly, a QPSK modulation-resultant signal is suited for detectingan amplitude distortion and a frequency offset.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 30), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 8PSK modulation. The first symbol in every frame (that is, the QPSKsymbol in every frame) is used by the receiver (see FIG. 32) as a pilotsymbol for estimating an amplitude distortion amount and a frequencyoffset amount. It should be noted that every pilot symbol also carries apart of the main information to be transmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and g signals of the RF portion 122to QPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 8PSK demodulation and outputs the8PSK-demodulation-resultant digital signal when the output I and Qsignals of the RF portion 122 represent a normal symbol different from apilot symbol.

The QPSK modulator 112J in the quadrature baseband modulator 112 of thetransmitter is designed to implement processes indicated below. Thephase of an i-th QPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th QPSK symbol in the I-Q plane is denoted by“φ_(i+1)”. The QPSK modulator 112J determines the phase “φ_(i+1)” of the(i+1)-th QPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the followingequation.θ_(i)+1=θ_(i)+1−φ_(i) (mod. 2π)  (35)The QPSK modulator 112J implements QPSK modulation providing four signalpoints which are spaced at equal angular intervals. The QPSK modulator112J assigns 2-bit sets of “00”, “01”, “10”, and “11” to the four signalpoints respectively. The QPSK modulator 112J outputs a pair ofmodulation-resultant I and Q signals to the switches 112D and 112E. TheQPSK modulator 112J includes a latch or a register for sampling andholding a pair of modulation-resultant I and Q signals which areselected by the switches 112D and 112E. The modulation-resultant I and Qsignals held by the latch or the register are periodically updated. TheQPSK modulator 112J outputs a pair of held modulation-resultant I and Qsignals to the 8PSK modulator 112A.

The 8PSK modulation implemented by the 8PSK modulator 112A provides 8different signal points to which 8 different logic states are assignedrespectively. For symbols following a QPSK symbol in every frame, the8PSK modulator 112A determines the assignment of the logic states to thesignal points on the basis of the signal point used by the QPSK symbol.The signal point used by the QPSK symbol is represented by a pair ofQPSK-modulation-resultant I and Q signals fed from the QPSK modulator112J. In the case where a signal point 2001 on the positive side of theI axis is used by a QPSK symbol, the 8PSK modulator 112A assigns 3-bitsets of “000”, “001”, “010”, “011”, “100”, “101”, “110”, and “111” inthe input digital signal to eight signal points 2002 for followingsymbols as shown in FIG. 72. In the case where a signal point 2001 onthe positive side of the Q axis is used by a QPSK symbol, the 8PSKmodulator 112A assigns 3-bit sets of “000”, “001”, “010”, “011”, “100”,“101”, “110”, and “111” in the input digital signal to eight signalpoints 2002 for following symbols as shown in FIG. 73. In the case wherea signal point 2001 on the negative side of the I axis is used by a QPSKsymbol, the 8PSK modulator 112A assigns 3-bit sets of “000”, “001”,“010”, “011”, “100”, “101”, “110”, and “111” in the input digital signalto eight signal points 2002 for following symbols as shown in FIG. 74.In the case where a signal point 2001 on the negative side of the Q axisis used by a QPSK symbol, the 8PSK modulator 112A assigns 3-bit sets of“000”, “001”, “010”, “011”, “100”, “101”, “110”, and “111” in the inputdigital signal to eight signal points 2002 for following symbols asshown in FIG. 75.

Twenty-First Embodiment

A twenty-first embodiment of this invention is similar to the sixteenthembodiment thereof except for design changes indicated hereinafter.

As shown in FIG. 76, a modulator (a quadrature baseband modulator) in atransmitter in the twenty-first embodiment of this invention includes aQPSK (quadrature phase shift keying) modulator 112J instead of the BPSKmodulator 112B (see FIG. 40). The QPSK modulator 112J implements QPSKmodulation providing signal points which are arranged in an I-Q plane asshown in FIG. 71.

As shown in FIG. 77, a quasi synchronous detector in a receiver in thetwenty-first embodiment of this invention includes a QPSK demodulator129G instead of the BPSK demodulator 129B (see FIG. 41). The QPSKdemodulator 129G implements demodulation inverse with respect to themodulation by the QPSK modulator 112J.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 30), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 2^(2m)-value QAM modulation. The first symbol in every frame (thatis, the QPSK symbol in every frame) is used by the receiver (see FIG.32) as a pilot symbol for estimating an amplitude distortion amount anda frequency offset amount. It should be noted that every pilot symbolalso carries a part of the main information to be transmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to QPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 122 represent a normal symbol differentfrom a pilot symbol.

The QPSK modulator 112J in the quadrature baseband modulator 112 of thetransmitter is designed to implement processes indicated below. Thephase of an i-th QPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th QPSK symbol in the I-Q plane is denoted by“φ_(i+1)”. The QPSK modulator 112J determines the phase “θ_(i+1)” of the(i+1)-th QPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the equation (35).The QPSK modulator 112J implements QPSK modulation providing four signalpoints which are spaced at equal angular intervals. The QPSK modulator112J assigns 2-bit sets of “00”, “01”, “10”, and “11” to four signalpoints in the x-y plane respectively. The QPSK modulator 112J outputs apair of modulation-resultant I and Q signals to the switches 112D and112E. The QPSK modulator 112J includes a latch or a register forsampling and holding a pair of modulation-resultant I and Q signalswhich are selected by the switches 112D and 112E. Themodulation-resultant I and Q signals held by the latch or the registerare periodically updated. The QPSK modulator 112J outputs a pair of heldmodulation-resultant I and Q signals to the 2^(2m)-value QAM modulator112F.

An example of the modulation implemented by the 2^(2m)-value QAMmodulator 112F is the 16-value QAM. The 16-value QAM by the 2^(2m)-valueQAM modulator 112F provides 16 different signal points to which 16different logic states are assigned respectively. For symbols followinga QPSK symbol in every frame, the 16-value QAM modulator 112F determinesthe assignment of the logic states to the signal points on the basis ofthe signal point used by the QPSK symbol. The signal point used by theQPSK symbol is represented by a pair of QPSK-modulation-resultant I andQ signals fed from the QPSK modulator 112J. In the case where a signalpoint 2101 on the positive side of the I axis is used by a GPSK symbol,the 16-value QAM modulator 112F assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal tosixteen signal points 2102 for following symbols as shown in FIG. 78. Inthe case where a signal point 2101 on the positive side of the Q axis isused by a QPSK symbol, the 16-value QAM modulator 112F assigns 4-bitsets of “0000”, “0001”, “0010”, . . . , “1110”, and “1111” in the inputdigital signal to sixteen signal points 2102 for following symbols asshown in FIG. 79. In the case where a signal point 2101 on the negativeside of the I axis is used by a QPSK symbol, the 16-value QAM modulator112F assigns 4-bit sets of “0000”, “0001”, “0010”, . . . , “1110”, and“111111” in the input digital signal to sixteen signal points 2102 forfollowing symbols as shown in FIG. 80. In the case where a signal point2101 on the negative side of the Q axis is used by a QPSK symbol, the16-value QAM modulator 112F assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal tosixteen signal points 2102 for following symbols as shown in FIG. 81.

Twenty-Second Embodiment

A twenty-second embodiment of this invention is similar to theseventeenth embodiment thereof except for design changes indicatedhereinafter.

As shown in FIG. 82, a modulator (a quadrature baseband modulator) in atransmitter in the twenty-second embodiment of this invention includes aQPSK (quadrature phase shift keying) modulator 112H instead of the BPSKmodulator 112B (see FIG. 47).

The QPSK modulator 112H implements QPSK modulation providing signalpoints which are arranged in an I-Q plane as shown in FIG. 55.

As shown in FIG. 83, a quasi synchronous detector in a receiver in thetwenty-second embodiment of this invention includes a QPSK demodulator129F instead of the BPSK demodulator 129B (see FIG. 48). The QPSKdemodulator 129F implements demodulation inverse with respect to themodulation by the QPSK modulator 112H.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 30), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols.

Here, N denotes a predetermined natural number. In every frame, thefirst symbol results from the QPSK modulation, and the second and latersymbols result from the 2^(2m)-value QAM modulation. The first symbol inevery frame (that is, the QPSK symbol in every frame) is used by thereceiver (see FIG. 32) as a pilot symbol for estimating an amplitudedistortion amount and a frequency offset amount. It should be noted thatevery pilot symbol also carries a part of the main information to betransmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to QPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 122 represent a normal symbol differentfrom a pilot symbol.

The QPSK modulator 112H in the quadrature baseband modulator 112 of thetransmitter is designed to implement processes indicated below. Thephase of an i-th QPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th QPSK symbol in the I-Q plane is denoted by“φ_(i+1)” The QPSK modulator 112H determines the phase “θ_(i+1)” of the(i+1)-th QPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the equation (32).The QPSK modulator 112H implements QPSK modulation providing four signalpoints which are spaced at equal angular intervals. The QPSK modulator112H assigns 2-bit sets of “00”, “01”, “10”, and “11” to four signalpoints in the x-y plane respectively. The QPSK modulator 112H outputs apair of modulation-resultant I and Q signals to the switches 112D and112E. The QPSK modulator 112H includes a latch or a register forsampling and holding a pair of modulation-resultant I and Q signalswhich are selected by the switches 112D and 112E. Themodulation-resultant I and Q signals held by the latch or the registerare periodically updated. The QPSK modulator 112H outputs a pair of heldmodulation-resultant I and Q signals to the 2^(2m)-value QAM modulator112G.

An example of the modulation implemented by the 2^(2m)-value QAMmodulator 112G is the 16-value QAM. The 16-value QAM by the 2^(2m)-valueQAM modulator 112G provides 16 different signal points to which 16different logic states are assigned respectively. For symbols followinga QPSK symbol in every frame, the 16-value QAM modulator 112G determinesthe assignment of the logic states to the signal points on the basis ofthe signal point used by the QPSK symbol. The signal point used by theQPSK symbol is represented by a pair of QPSK-modulation-resultant I andQ signals fed from the QPSK modulator 112H. In the case where apositive-I positive-Q signal point 2201 is used by a QPSK symbol, the16-value QAM modulator 112G assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal tosixteen signal points 2202 for following symbols as shown in FIG. 84. Inthe case where a negative-I positive-Q signal point 2201 is used by aQPSK symbol, the 16-value QAM modulator 112G assigns 4-bit sets of“0000”, “0001”, “0010”, “1110”, and “1111” in the input digital signalto sixteen signal points 2202 for following symbols as shown in FIG. 85.In the case where a negative-I negative-Q signal point 2201 is used by aQPSK symbol, the 16-value QAM modulator 112G assigns 4-bit sets of“0000”, “0001”, “0010”, . . . , “1110”, and 1“1111” in the input digitalsignal to sixteen signal points 2202 for following symbols as shown inFIG. 86. In the case where a positive-I negative-Q signal point 2201 isused by a QPSK symbol, the 16-value QAM modulator 112G assigns 4-bitsets of “0000”, “0001”, “0010”, . . . , “1110”, and “1111” in the inputdigital signal to sixteen signal points 2202 for following symbols asshown in FIG. 87.

Twenty-Third Embodiment

A twenty-third embodiment of this invention is similar to theseventeenth embodiment thereof except for design changes indicatedhereinafter.

As shown in FIG. 88, a modulator (a quadrature baseband modulator) in atransmitter in the twenty-third embodiment of this invention includes aQPSK (quadrature phase shift keying) modulator 112J instead of the BPSKmodulator 112B (see FIG. 47). The QPSK modulator 112J implements QPSKmodulation providing signal points which are arranged in an I-Q plane asshown in FIG. 71.

As shown in FIG. 89, a quasi synchronous detector in a receiver in thetwenty-second embodiment of this invention includes a QPSK demodulator129G instead of the BPSK demodulator 129B (see FIG. 48). The QPSKdemodulator 129G implements demodulation inverse with respect to themodulation by the QPSK modulator 112J.

A pair of the I signal and the Q signal outputted from the quadraturebaseband modulator in the transmitter (see FIG. 30), or the RF signaloutputted from the RF portion in the transmitter is composed of a streamof frames each having N successive symbols. Here, N denotes apredetermined natural number. In every frame, the first symbol resultsfrom the QPSK modulation, and the second and later symbols result fromthe 2^(2m)-value QAM modulation. The first symbol in every frame (thatis, the QPSK symbol in every frame) is used by the receiver (see FIG.32) as a pilot symbol for estimating an amplitude distortion amount anda frequency offset amount. It should be noted that every pilot symbolalso carries a part of the main information to be transmitted.

In the receiver (see FIG. 32), the calculator 125 separates pilotsymbols (first symbols in frames) from the output I and Q signals of theRF portion 122 in response to a signal (a frame and symbol sync signal)having a period corresponding to N symbols. The calculator 125 estimatesan amplitude distortion amount from the separated pilot symbols.Similarly, the calculator 126 separates pilot symbols (first symbols inframes) from the output I and Q signals of the RF portion 122 inresponse to a signal (a frame and symbol sync signal) having a periodcorresponding to N symbols. The calculator 126 estimates a frequencyoffset amount from the separated pilot symbols.

The quasi synchronous detector 129 in the receiver (see FIG. 32) isdesigned to implement the following processes. The quasi synchronousdetector 129 subjects the output I and Q signals of the RF portion 122to QPSK demodulation and outputs the QPSK-demodulation-resultant digitalsignal when the output I and Q signals of the RF portion 122 represent apilot symbol. The quasi synchronous detector 129 subjects the output Iand Q signals of the RF portion 122 to 2^(2m)-value QAM demodulation andoutputs the QAM-demodulation-resultant digital signal when the output Iand Q signals of the RF portion 122 represent a normal symbol differentfrom a pilot symbol.

The QPSK modulator 112J in the quadrature baseband modulator 112 of thetransmitter is designed to implement processes indicated below. Thephase of an i-th QPSK symbol in the I-Q plane is denoted by “φ_(i)”, andthe phase of an (i+1)-th QPSK symbol in the I-Q plane is denoted by“φ_(i+1)” The QPSK modulator 112H determines the phase “θ_(i+1)” of the(i+1)-th QPSK symbol in an x-y plane on the basis of the differencebetween the phases “φ_(i)” and “φ_(i+1)” according to the equation (35).The QPSK modulator 112J implements QPSK modulation providing four signalpoints which are spaced at equal angular intervals. The QPSK modulator112J assigns 2-bit sets of “00”, “01”, “10”, and “11” to four signalpoints in the x-y plane respectively. The QPSK modulator 112J outputs apair of modulation-resultant I and Q signals to the switches 112D and112E. The QPSK modulator 112J includes a latch or a register forsampling and holding a pair of modulation-resultant I and Q signalswhich are selected by the switches 112D and 112E. Themodulation-resultant I and Q signals held by the latch or the registerare periodically updated. The QPSK modulator 112J outputs a pair of heldmodulation-resultant I and Q signals to the 2^(2m)-value QAM modulator112G.

An example of the modulation implemented by the 2^(2m)-value QAMmodulator 112G is the 16-value QAM. The 16-value QAM by the 2^(2m)-valueQAM modulator 112G provides 16 different signal points to which 16different logic states are assigned respectively. For symbols followinga QPSK symbol in every frame, the 16-value QAM modulator 112G determinesthe assignment of the logic states to the signal points on the basis ofthe signal point used by the QPSK symbol. The signal point used by theQPSK symbol is represented by a pair of QPSK-modulation-resultant I andQ signals fed from the QPSK modulator 112J. In the case where a signalpoint 2301 on the positive side of the I axis is used by a QPSK symbol,the 16-value QAM modulator 112G assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal tosixteen signal points 2302 for following symbols as shown in FIG. 90. Inthe case where a signal point 2301 on the positive side of the Q axis isused by a QPSK symbol, the 16-value QAM modulator 112G assigns 4-bitsets of “0000”, “0001”, “0010”, . . . , “1110”, and “1111” in the inputdigital signal to sixteen signal points 2302 for following symbols asshown in FIG. 91. In the case where a signal point 2301 on the negativeside of the I axis is used by a QPSK symbol, the 16-value QAM modulator112G assigns 4-bit sets of “0000”, “0001”, “0010”, . . . , “1110”, and“1111” in the input digital signal to sixteen signal points 2302 forfollowing symbols as shown in FIG. 92. In the case where a signal point2301 on the negative side of the Q axis is used by a QPSK symbol, the16-value QAM modulator 112G assigns 4-bit sets of “0000”, “0001”,“0010”, . . . , “1110”, and “1111” in the input digital signal tosixteen signal points 2302 for following symbols as shown in FIG. 93.

SIMULATION

Simulation was executed by a computer. During the simulation, normalsymbols were made on the basis of 16-value QAM while pilot symbols weremade on the basis of QPSK modulation according to this invention. Thenormal symbols and the pilot symbols were combined into a symbol streamin a way based on this invention. In the symbol stream, the number ofnormal symbols between pilot symbols (that is, a data symbol length) wasequal to a given natural number “n” while each of the separate pilotsymbols was equal to “1” in length. The given natural number “n” was“1”, “7”, or “15”. Accordingly, symbol streams of three types weregenerated. During the simulation, each of the first-type symbol stream,the second-type symbol stream, and the third-type symbol stream wastransmitted from a transmitter to a receiver. In the receiver, normalsymbols were subjected to quasi synchronous detection using 16-value QAMdemodulation while pilot symbols were subjected to delayed detectionusing QPSK demodulation. Regarding the transmission of each of thefirst-type symbol stream, the second-type symbol stream, and thethird-type symbol stream, the bit error rate was calculated at a varyingratio of the 1-bit signal energy “Eb” to the noise power density “N0”.In the case where the given natural number “n” was equal to “1”, as theratio of the 1-bit signal energy “Eb” to the noise power density “N0”increased, the calculated bit error rate decreased along the curve D1 ofFIG. 94. In the case where the given natural number “n” was equal to“7”, as the ratio of the 1-bit signal energy “Eb” to the noise powerdensity “N0” increased, the calculated bit error rate decreased alongthe curve D7 of FIG. 94. In the case where the given natural number “n”was equal to “15”, as the ratio of the 1-bit signal energy “Eb” to thenoise power density “N0” increased, the calculated bit error ratedecreased along the curve D15 of FIG. 94.

As comparative examples, similar simulation was implemented on aprior-art system. Specifically, normal symbols were made on the basis of16-value QAM while a signal point corresponding to a maximum amplitudewas used as pilot symbols. The normal symbols and the pilot symbols werecombined into a symbol stream in a prior-art way. In the symbol stream,the number of normal symbols between pilot symbols (that is, a datasymbol length) was equal to a given natural number “n” while each of theseparate pilot symbols was equal to “1” in length. The given naturalnumber “n” was “1”, “7”, or “15”. Accordingly, symbol streams of threetypes were generated. Each of the first-type symbol stream, thesecond-type symbol stream, and the third-type symbol stream wastransmitted from a transmitter to a receiver. In the receiver, thetransmitted symbol stream was subjected to quasi synchronous detectionusing 16-value QAM demodulation. Regarding the transmission of each ofthe first-type symbol stream, the second-type symbol stream, and thethird-type symbol stream, the bit error rate was calculated at a varyingratio of the 1-bit signal energy “Eb” to the noise power density “N0”.In the case where the given natural number “n” was equal to “1”, as theratio of the 1-bit signal energy “Eb” to the noise power density “N0”increased, the calculated bit error rate decreased along the curve E1 ofFIG. 94. In the case where the given natural number “n” was equal to“7”, as the ratio of the 1-bit signal energy “Eb” to the noise powerdensity “N0” increased, the calculated bit error rate decreased alongthe curve E7 of FIG. 94. In the case where the given natural number “n”was equal to “15”, as the ratio of the 1-bit signal energy “Eb” to thenoise power density “N0” increased, the calculated bit error ratedecreased along the curve E15 of FIG. 94.

As shown in FIG. 94, the bit error rates (the curves D1, D7, and D15) inthis invention are better than the corresponding prior-art bit errorrates (the curves E1, E7, and E15).

1. A modulation method for modulating an input digital signal into amulti-value symbol stream, the modulation method comprising: generatinga first multi-value modulation signal having first multi-value symbolsfrom the input digital signal with a first modulator; generating asecond modulation signal containing second multi-value symbols from apart of information of said input digital signal by using a secondmodulator, a channel distortion of said first multi-value modulationsignal being estimated by using only said second modulation signal todemodulate said first multi-value modulation signal in a receiver; andinserting said second multi-value symbols into said first multi-valuesymbols to produce said multi-value symbol stream such that anarrangement of signal points corresponding to the first multi-valuesymbols of the first quadrature baseband signal is determined based onan arrangement of signal points corresponding to the second multi-valuesymbols of the second modulation signal in said multi-value symbolstream, and the resultant multi-value symbols constitute saidmulti-value symbol stream.
 2. A transmission apparatus comprising: afirst multi-value modulation system for subjecting an input digitalsignal to first modulation and outputting a first quadrature basebandsignal; and a second multi-value modulation system for subjecting theinput digital signal to second modulation and outputting a secondquadrature baseband signal, a channel distortion of said firstquadrature baseband signal being estimated by using only said secondquadrature baseband signal to demodulate said first quadrature basebandsignal in a receiver, wherein said second quadrature baseband signal isregularly inserted into the first quadrature baseband signal to producea multi-value symbol stream such that an arrangement of signal pointscorresponding to first multi-value symbols of the first quadraturebaseband signal is determined based on an arrangement of signal pointscorresponding to second multi-value symbols of the second quadraturebaseband signal in the multi-value symbol stream.
 3. The modificationmethod according to claim 1, wherein the second modulation signal isgenerated based on phase shift keying in the second modulator.
 4. Thetransmission apparatus according to claim 2, wherein the secondmulti-value modulation system is adapted to subject the input digitalsignal to quadrature phase shift keying as the second modulation.